Method and program for calculating potential, current, and peripheral electromagnetic field in electric circuit

ABSTRACT

It is possible to comprehensively calculate a potential and a current of a transmission line in an electric circuit, a potential and a current of an element, and an electromagnetic field including noise generated from the electric circuit. A computer performs a circuit configuration inputting step of inputting a circuit configuration of a distributed constant circuit and a lumped constant circuit and an initial value of each variable, and a calculating step of obtaining a scalar potential and a current in a multi-conductor transmission line, a scalar potential and a voltage in an element, and an electromagnetic radiation amount by, under the circuit configuration and the initial value, solving a basic equation of a transmission theory using a boundary condition formula at x=0 and w which are the boundary between the distributed constant circuit and the lumped constant circuit.

TECHNICAL FIELD

The present invention relates to a method and a program for calculating a potential, a current, and a peripheral electromagnetic field, which comprehensively calculate a potential and a current of a transmission line in an electric circuit, a potential and a current of an element, and a peripheral electromagnetic field including noise generated inside and outside the electric circuit.

BACKGROUND ART

Conventionally, the investigation of an electromagnetic field around a device by simulation is performed in order of (1) input of information of a circuit constituting the device, (2) calculation of a potential and a current of a transmission line or an element based on a lumped constant circuit theory or a distributed constant circuit theory related to a multiconductor transmission line (see Non Patent Document 1), and (3) calculation of an electromagnetic field. However, in practice, the potential and current of the transmission line and the element and the peripheral electromagnetic field interact with each other, and the electromagnetic field cannot be calculated with high accuracy in a conventional electromagnetic field calculation method which does not consider the interaction. Therefore, it was common to take countermeasures such as empirically known methods and symptomatic treatment for electromagnetic noise that has occurred as a result after designing a circuit based on the calculation result by simulation.

Under such circumstances, there was proposed a new transmission theory for comprehensively calculating a potential and a current of a transmission line, a potential and a current of an element, and an electromagnetic field including noise generated there from by fusing a multiconductor transmission line theory and an antenna theory (see Non Patent Document 2).

Equations (1) and (2) showing a conventional multiconductor transmission line theory shown in Non Patent Document 1 were created from phenomenological considerations.

[Math.  1] $\begin{matrix} {\frac{\partial{I_{j}\left( {t,x} \right)}}{\partial x} = {{- \Sigma_{j = 2}^{n}}{C_{ij} \cdot {\frac{\partial{V_{j}\left( {t,x} \right)}}{\partial t}\left\lbrack {{Math}.\mspace{14mu} 2} \right\rbrack}}}} & (1) \\ {\frac{\partial{V_{i}\left( {t,x} \right)}}{\partial x} = {{- \Sigma_{j = 2}^{n}}{L_{ij} \cdot \frac{\partial{I_{j}\left( {t,x} \right)}}{\partial t}}}} & (2) \end{matrix}$

(V_(i) is a potential difference (voltage) from a reference line (transmission line 1) of a transmission line i among n transmission lines, is a current flowing through the transmission line i, C_(ij) and L_(ij) are an electrical capacitance and an induction coefficient between transmission lines i and j respectively)

On the other hand, the new transmission theory incorporates the antenna theory into the multiconductor transmission line theory, and the basic equation is directly derived from Maxwell's equation. Hereinafter, the outline of the new transmission theory shown in Non Patent Document 2 will be described.

In the electric circuit, the transmission line is used for carrying electricity. However, the energized transmission line also functions as an antenna, and radiation of electromagnetic waves from the antenna is discussed from Maxwell's equation. Therefore, the relationship between multiconductor transmission line theory and the electromagnetic radiation from the multiconductor transmission line constituting the electric circuit is discussed based on the antenna theory given by Maxwell's equations.

It is well known that Maxwell's equation describes electromagnetic waves. A delay potential derived from the Maxwell equation at a position represented by a vector r_(v) at time t, that is, a scalar potential U (t, r_(v)) and a vector potential A_(v)(t, r_(v)) can be written as follows.

[Math.  3] $\begin{matrix} {{U\left( {t,r_{v}} \right)} = {\frac{1}{4{\pi ɛ}}{\int{d^{3}r_{v}^{\prime}{\frac{q\left( {\left. {t -} \middle| {r_{v} - r_{v}^{\prime}} \middle| {\text{/}c} \right.,r_{v}^{\prime}} \right)}{\left| {r_{v} - r_{v}^{\prime}} \right|}\left\lbrack {{Math}.\mspace{14mu} 4} \right\rbrack}}}}} & (3) \\ {{A_{v}\left( {t,r_{v}} \right)} = {\frac{\mu}{4\pi}{\int{d^{3}r_{v}^{\prime}\frac{i_{v}\left( {\left. {t -} \middle| {r_{v} - r_{v}^{\prime}} \middle| {\text{/}c} \right.,r_{v}^{\prime}} \right)}{\left| {r_{v} - r_{v}^{\prime}} \right|}}}}} & (4) \end{matrix}$

(ε is a permittivity, μ is a permeability, c is the speed of light, and t′ and r_(v)′ are a time prior to time t and a position at time t′ satisfying the relationship t′=t−|r_(v)−r_(v)′|/c)

That is, the scalar potential U(t, r_(v)) and the vector potential A_(v)(t, r_(v)) at the time t are based on a charge density q(t′, r_(v)′) and a current density vector i_(v)(t′, r_(v)′) at the time t′ and the position r_(v)′.

Here, for each of the n parallel transmission lines having a length w, when assumed that charge and current are gathered at the center of the electric wire and the charge and the current are integrated (∫ds) by a cross-sectional area at a position x in a longitudinal direction of the transmission line, the charge Q_(i)(t, x) and the current I_(i)(t, x) per unit length of the i-th transmission line i at the time t and the position x are given. by Q_(i)(t, x)=∫ds·q_(i)(t, r_(v)), and I_(i)(t, x)=∫ds·i_(i)(t, r_(v)). In addition, because of the axial symmetry, the direction of the current can be regarded as only the direction of the transmission line, that is, the x direction, so that the vector potential A_(v)(t, r_(v)) can be expressed simply as A(t, x). Then, when the distance between the center of the transmission line i and the adjacent transmission line j is d_(ij), the scalar potential U_(i)(t, x) and the vector potential A_(i)(t, x) on the surface of each transmission line distant from the position x of the transmission line i by the distance d_(ij) can be described as follows.

[Math.  5] $\begin{matrix} {{U_{i}\left( {t,x} \right)} = {\frac{1}{4{\pi ɛ}}\Sigma_{j = 1}^{n}{\int_{0}^{w}{{dx}^{\prime}{\frac{Q_{j}\left( {{t - {\sqrt{\left( {x - x^{\prime}} \right)^{2} + d_{ij}^{2}}\text{/}c}},x^{\prime}} \right)}{\sqrt{\left( {x - x^{\prime}} \right)^{2} + d_{ij}^{2}}}\left\lbrack {{Math}.\mspace{14mu} 6} \right\rbrack}}}}} & (5) \\ {{A_{i}\left( {t,x} \right)} = {\frac{\mu}{4\pi}\Sigma_{j = 1}^{n}{\int_{0}^{w}{{dx}^{\prime}\frac{I_{j}\left( {{t - {\sqrt{\left( {x - x^{\prime}} \right)^{2} + d_{ij}^{2}}\text{/}c}},x^{\prime}} \right)}{\sqrt{\left( {x - x^{\prime}} \right)^{2} + d_{ij}^{2}}}}}}} & (6) \end{matrix}$

From these equations, the electromagnetic field on the surface of the transmission line can be obtained, and the electromagnetic field generated around the transmission line can be obtained from the obtained electromagnetic field of the transmission line surface by the theory of electromagnetism.

d_(ij) generally takes a very small value in the electric circuit. At this time, the integrands of Equations (5) and (6) have a divergent peak near x′=x, and need to be handled separately for the portion that does not contributes there around and the other portions. Therefore, when approximating to Q_(j)(t, x′)=Q_(j)(t, x) and I_(j)(t, x′)=I_(j)(t, x), as shown in the first term of Equations (7) and (8), it is possible to put Q_(j)(t, x) and I_(j)(t, x) outside the integral and analytically calculate the integral of the remaining x′. On the other hand, the second term in Equations (7) and (8) becomes a part that can be handled numerically by removing the diverging part.

     [Math.  7] $\begin{matrix} {{{U_{i}\left( {t,x} \right)} = {\frac{1}{4{\pi ɛ}}{{\Sigma_{j = 1}^{n}\left\lbrack {{\int_{0}^{w}{{dx}^{\prime}{\frac{1}{\sqrt{\left( {x - x^{\prime}} \right)^{2} + d_{ij}^{2}}} \cdot {Q_{j}\left( {t,x} \right)}}}} + {\int_{0}^{w}{{dx}^{\prime}\frac{{Q_{j}\left( {{t - {\sqrt{\left( {x - x^{\prime}} \right)^{2} + d_{ij}^{2}}\text{/}c}},x^{\prime}} \right)} - {Q_{j}\left( {t,x} \right)}}{\sqrt{\left( {x - x^{\prime}} \right)^{2} + d_{ij}^{2}}}}}} \right\rbrack}\mspace{76mu}\left\lbrack {{Math}.\mspace{14mu} 8} \right\rbrack}}}\mspace{25mu}} & (7) \\ {{A_{i}\left( {t,x} \right)} = {\frac{\mu}{4\pi}{\Sigma_{j = 1}^{n}\left\lbrack {{\int_{0}^{w}{{dx}^{\prime}{\frac{1}{\sqrt{\left( {x - x^{\prime}} \right)^{2} + d_{ij}^{2}}} \cdot {I_{j}\left( {t,x} \right)}}}} + {\int_{0}^{w}{{dx}^{\prime}\frac{{I_{j}\left( {{t - {\sqrt{\left( {x - x^{\prime}} \right)^{2} + d_{ij}^{2}}\text{/}c}},x^{\prime}} \right)} - {I_{j}\left( {t,x} \right)}}{\sqrt{\left( {x - x^{\prime}} \right)^{2} + d_{ij}^{2}}}}}} \right\rbrack}}} & (8) \end{matrix}$

Since d_(ij)<<w in general, d_(ij)=0 can be set except for the case of x′=x. Therefore, the second term of Equations (7) and (8) can be expressed by using the total charge Q_(t) and the total current I_(t) of the n transmission lines, and Equations (7) and (8) can be expressed as Equations (9) and (11) and Equations (10) and (12), respectively.

[Math.  9] $\begin{matrix} {{U_{i}\left( {t,x} \right)} = {{\Sigma_{j = 1}^{n}{P_{ij} \cdot {Q_{j}\left( {t,x} \right)}}} + {{{\,^{\sim}U}\left( {t,x} \right)}\left\lbrack {{Math}.\mspace{14mu} 10} \right\rbrack}}} & (9) \\ {{A_{i}\left( {t,x} \right)} = {{\Sigma_{j = 1}^{n}{L_{ij} \cdot {I_{j}\left( {t,x} \right)}}} + {{{\,^{\sim}A}\left( {t,x} \right)}\left\lbrack {{Math}.\mspace{14mu} 11} \right\rbrack}}} & (10) \\ {{{\,^{\sim}U}\left( {t,x} \right)} = {\frac{1}{4{\pi ɛ}}{\int_{0}^{w}{{dx}^{\prime}{\frac{{Q_{t}\left( {{t - {\sqrt{\left| {x - x^{\prime}} \right|}\text{/}c}},x^{\prime}} \right)} - {Q_{t}\left( {t,x} \right)}}{\left| {x - x^{\prime}} \right|}\left\lbrack {{Math}.\mspace{14mu} 12} \right\rbrack}}}}} & (11) \\ {{{\,^{\sim}A}\left( {t,x} \right)} = {\frac{\mu}{4\pi}{\int_{0}^{w}{{dx}^{\prime}\frac{{I_{t}\left( {{t - {\sqrt{\left| {x - x^{\prime}} \right|}\text{/}c}},x^{\prime}} \right)} - {I_{t}\left( {t,x} \right)}}{\left| {x - x^{\prime}} \right|}}}}} & (12) \end{matrix}$

(P_(i) is a potential coefficient between the transmission lines i and j, an element of an inverse matrix of a matrix having these as an element corresponds to a reciprocal number of the electrostatic capacitance C_(ij). L_(ij) is an induction coefficient between the transmission lines i and j.)

˜U(t, x) in Equation (11) and ˜A(t, x) in Equation (12) corresponding to the second term in Equations (7) and (8) respectively include a potential delay, which represents an electromagnetic wave emission and absorption process, that is, an antenna process (see Non Patent Document 2).

The electromagnetic potential generated from these charges and currents affects the charge current in the transmission line. In macroscopic systems dealing with electromagnetics, it is possible to use the phenomenological Ohm's law which does not directly handle charge motion and describes its average behavior. Specifically, when a resistance R_(i) determined from the property of the transmission line i is given, the current I_(i)(t, x) at the position when the electric field E(t, x) is given is expressed by

E _(i)(t,x)=R _(i) ·I _(i)(t,x)   (13).

By expressing Equation (13) by potential, the following equation that the current is determined when the electromagnetic potential is given is obtained.

[Math.  13] $\begin{matrix} {{{- \frac{\partial{U_{i}\left( {t,x} \right)}}{\partial x}} - \frac{\partial{A_{i}\left( {t,x} \right)}}{\partial t}} = {R_{i} \cdot {I_{i}\left( {t,x} \right)}}} & (14) \end{matrix}$

Furthermore, the equation o£ continuity between Q and I is considered.

[Math.  14] $\begin{matrix} {{\frac{\partial{Q_{i}\left( {t,x} \right)}}{\partial x} + \frac{\partial{I_{i}\left( {t,x} \right)}}{\partial t}} = 0} & (15) \end{matrix}$

Since four Equations (9), (10), (14), and (15) are given to four variables of the two potentials (U, A) and the two charge currents (Q, I), it is possible to solve these equations by giving appropriate boundary conditions.

By calculating the time derivative of the potentials of Equations (9) and (10) and then eliminating A and Q by using Equations (14) and (15), two Equations (16) and (17) are obtained. These two partial differential equations are basic equations of a new transmission theory incorporating an antenna theory into a multiconductor transmission line theory, which is directly derived from Maxwell's equation. Both equations are equations expressing the amount of change in scalar potential, that is, the amount of change in potential, by using the amount of change in current.

[Math.  15] $\begin{matrix} {\frac{\partial{U_{i}\left( {t,x} \right)}}{\partial t} = {{{- \Sigma_{j = 1}^{n}}{P_{ij} \cdot \frac{\partial{I_{j}\left( {t,x} \right)}}{\partial x}}} + {\frac{\partial{{\,^{\sim}U}\left( {t,x} \right)}}{\partial t}\left\lbrack {{Math}.\mspace{14mu} 16} \right\rbrack}}} & (16) \\ {\frac{\partial{U_{i}\left( {t,x} \right)}}{\partial x} = {{{- \Sigma_{j = 1}^{n}}{L_{ij} \cdot \frac{\partial{I_{j}\left( {t,x} \right)}}{\partial t}}} - \frac{\partial{{\,^{\sim}A}\left( {t,x} \right)}}{\partial t} - {R_{i} \cdot {I_{i}\left( {t,x} \right)}}}} & (17) \end{matrix}$

The basic equation of the conventional multiconductor transmission line theory shown in Equations (1) and (2) can be rewritten on the same left side as in Equations (16) and (17) by using the potential coefficient P_(ij) and potential (see Non Patent Document 3).

[Math.  17] $\begin{matrix} {\frac{\partial{U_{i}\left( {t,x} \right)}}{\partial t} = {{- \Sigma_{j = 1}^{n}}{P_{ij} \cdot {\frac{\partial{I_{j}\left( {t,x} \right)}}{\partial x}\left\lbrack {{Math}.\mspace{14mu} 18} \right\rbrack}}}} & (18) \\ {\frac{\partial{U_{i}\left( {t,x} \right)}}{\partial x} = {{- \Sigma_{j = 1}^{n}}{L_{ij} \cdot \frac{\partial{I_{j}\left( {t,x} \right)}}{\partial t}}}} & (19) \end{matrix}$

As can be seen by comparing the right side of Equations (16) and (17) with the right side of Equations (18) and (19), the first term on the right side of Equations (16) and (17) coincides with the right side of Equations (18) and (19). That is, Equations (16) and (17), which are basic equations of new transmission theory, include Equations (18) and (19) of the conventional multi-conductor transmission theory created from phenomenological considerations. Equations (16) and (17) additionally include the antenna term ˜U(t, x) and ˜A(t, x) representing the antenna process, respectively.

PRIOR ART REFERENCES Non Patent Document

-   Non Patent Document 1: Clayton R. Paul, “Analysis of Multiconductor     Transmission Lines”, Wiley-Inter-Science, 2008 -   Non Patent Document 2: Hiroshi Toki and Kenji Sato, “Multiconductor     Transmission-Line Theory with Electromagnetic Radiation”, Journal of     the Physical Society of Japan, January 2012, Vol. 81, 014201 -   Non Patent document 3: Hiroshi Toki and Kenji Sato, “Three Conductor     Transmission Line Theory and Origin of Electromagnetic Radiation and     Noise”, Journal of the Physical Society of Japan, January 2009, Vol.     78, 094201

SUMMARY OF THE INVENTION Problems to be Solved by the Invention

The basic equations of the new transmission theory described as the background art can be solved by giving appropriate boundary conditions. However, the method of setting the boundary conditions has been clarified only in the limited cases such as one resistor and one capacitor, and a specific calculation method under the boundary condition to which an arbitrary lumped constant circuit is connected has not been clarified.

An object of the present invention to provide an efficient calculation method under the boundary condition while giving an appropriate boundary condition to a basic equation of a new transmission theory and thus to provide a method and a program of calculating a potential, a current, and a peripheral electromagnetic field in an electric circuit, which can comprehensively calculate a potential and a current of a multi-conductor transmission line constituting a distributed constant circuit, a potential and a current of an element constituting a lumped constant circuit connected to the multi-conductor transmission line, and an electromagnetic field including noise generated inside and outside the electric circuit.

Means for Solving the Problems

(1) There is provided a method for calculating a potential, a current, and a peripheral electromagnetic field in an electric circuit, which causes a computer to calculate a potential and a current in a multi-conductor transmission line constituting a distributed constant circuit, a potential and a current in an element constituting a lumped constant circuit connected to the multi-conductor transmission line, and an electromagnetic radiation amount from each circuit, the method including: a circuit configuration inputting step of inputting a circuit configuration of the distributed constant circuit and the lumped constant circuit and an initial value of each variable; and a calculating step of obtaining the potential and the current in the multi-conductor transmission line, the potential and the current in the element, and the electromagnetic radiation amount by solving:

under the circuit configuration and the initial value, the following basic equations of new transmission theory:

[Math.  19] $\begin{matrix} {\frac{\partial{U_{i}\left( {t,x} \right)}}{\partial t} = {{{- \Sigma_{j = 1}^{n}}{P_{ij} \cdot \frac{\partial{I_{j}\left( {t,{xc}} \right)}}{\partial x}}} + {\frac{\partial{{\,^{\sim}U}\left( {t,x} \right)}}{\partial t}\left\lbrack {{Math}.\mspace{14mu} 20} \right\rbrack}}} & (20) \\ {\frac{\partial{U_{i}\left( {t,x} \right)}}{\partial x} = {{{- \Sigma_{j = 1}^{n}}{L_{ij} \cdot \frac{\partial{I_{j}\left( {t,x} \right)}}{\partial t}}} - \frac{\partial{{\,^{\sim}A}\left( {t,x} \right)}}{\partial t} - {R_{i} \cdot {{I_{i}\left( {t,x} \right)}\left\lbrack {{Math}.\mspace{14mu} 21} \right\rbrack}}}} & (21) \\ {{{\,^{\sim}U}\left( {t,x} \right)} = {\frac{1}{4{\pi ɛ}}{\int_{0}^{w}{{dx}^{\prime}{\frac{{Q_{t}\left( {{t - {\sqrt{\left| {x - x^{\prime}} \right|}\text{/}c}},x^{\prime}} \right)} - {Q_{t}\left( {t,x} \right)}}{\left| {x - x^{\prime}} \right|}\left\lbrack {{Math}.\mspace{14mu} 22} \right\rbrack}}}}} & (22) \\ {{{\,^{\sim}A}\left( {t,x} \right)} = {\frac{\mu}{4\pi}{\int_{0}^{w}{{dx}^{\prime}\frac{{I_{t}\left( {{t - {\sqrt{\left| {x - x^{\prime}} \right|}\text{/}c}},x^{\prime}} \right)} - {I_{t}\left( {t,x} \right)}}{\left| {x - x^{\prime}} \right|}}}}} & (23) \end{matrix}$

using a boundary condition formula at x=0 and w which are boundaries between the distributed constant circuit and the lumped constant circuit:

U _(i)(t,x)−U _(j)(t,x)=V _(ij)(t)+Z _(ij) ·Δ·I _(ij)(t)   (24), and

Kirchhoff's current law, that is, a summation formula in which an algebraic sum of branch currents of all the branches flowing into one node is zero, that is, a current flowing out from the node is positive and a current entering the node is negative:

α·I _(i)(t,x)+Σ_(j(≠i)) I _(ij)(t)=0   (25)

(t is a time, x and x′ are positions on each transmission line (x>x′), i, j (=1, 2, . . . , n) is the number of each transmission line, U_(i)(t, x) and A_(i)(t, x) are scalar potential (potential) and vector potential of a transmission line i at time t and a position x, respectively, I_(j)(t, x) is a current flowing in a transmission line j at the time t and the position x, P_(ij) and L_(ij) are a potential coefficient and an induction coefficient between the transmission lines i and j respectively, R_(i) is a resistance per unit length of the transmission line i, ˜U(t, x) and ˜A(t, x) are antenna terms indicating the electromagnetic radiation amount at the time t and the position x, ε is a permittivity, μ is a permeability, Q_(t)(t, x) and I_(t)(t, x) are a charge and a current of all transmission lines at the time t and the position x, V_(ij)(t) is a power supply voltage connected between the nodes i, j (≠i) at the time t on the lumped constant circuit side, I_(ij)(t) is a current flowing from the node i to the node j (≠i) at the time t on the lumped constant circuit side, Z_(ij) is a load connected between the nodes i, j (≠i), Δ is 1 when Z_(ij)=R_(ij), d/dt when Z_(ij)=L_(ij), and (d/dt)⁻¹ when Z_(ij)=1/C_(i j), and α is 1 when x=0 and −1 when x=w).

In this way, by giving the boundary conditions to the basic equations of the new transmission theory, it is possible to comprehensively calculate the potential and current in the multi-conductor transmission line constituting the constant circuit, the potential and the current in the element constituting the lumped constant circuit connected to the multi-conductor transmission line, and the electromagnetic fields including noise generated from each circuit.

(2) The calculation of the basic equations of the new transmission theory can be performed efficiently by using the Finite Difference Time Domain (FDTD) method. In the boundary condition between the transmission line part and the lumped circuit part, the calculation is possible by using the result calculated by FDTD and the theory based on the circuit theory used on lumped constant side. Specifically, on the lumped constant side, Kirchhoff's voltage law, Kirchhoff s current law, and the voltage-current characteristics of the element can be used.

(3) In the case of performing the calculation by using the FDTD method, when a scalar potential at a position x=k·Δx (k=0, 1, . . . , N, w=N ·Δx) and time t=m·Δt (m=0, 1, . . . , arbitrary) on the transmission line i is U_(k) ^(m), a current is denoted as I_(k) ^(m), Uv_(k) ^(m) is a vector with U_(k) ^(m) as an element for each transmission line i, Iv_(k) ^(m) is a vector whose elements are I_(k) ^(m) for each transmission line i, P_(d) is a matrix whose elements are P_(ij), L_(d) is a matrix whose elements are L_(ij), and R_(d) is a matrix whose diagonal element is R_(i), Equation (20) may be discretized into

[Math.  23] $\begin{matrix} {\frac{{Uv}_{k}^{m + 1} - {Uv}_{k}^{m}}{\Delta \; t} = {{{- P_{d}}\frac{{Iv}_{k + {1\text{/}2}}^{m + {1\text{/}2}} - {Iv}_{k - {1\text{/}2}}^{m + {1\text{/}2}}}{\Delta \; x}} + \frac{{{}_{}^{}{}_{}^{m + 1}} - {{}_{}^{}{}_{}^{}}}{\Delta \; t}}} & (26) \end{matrix}$

and Equation (21) may be discretized into

     [Math.  24] $\begin{matrix} {\frac{{Uv}_{k + 1}^{m + 1} - {Uv}_{k}^{m + 1}}{\Delta \; x} = {{{- L_{d}}\frac{{Iv}_{k + {1\text{/}2}}^{m + {3\text{/}2}} - {Iv}_{k + {1\text{/}2}}^{m + {1\text{/}2}}}{\Delta \; t}} - \frac{{{}_{}^{}{}_{k + {1\text{/}2}}^{m + {1\text{/}2}}} - {{}_{}^{}{}_{k + {1\text{/}2}}^{m - {1\text{/}2}}}}{\Delta \; t} - {R_{d}\frac{{Iv}_{k + {1\text{/}2}}^{m + {3\text{/}2}} - {Iv}_{k + {1\text{/}2}}^{m + {1\text{/}2}}}{2}}}} & (27) \end{matrix}$

(4) When Zc_(d) is a matrix having a characteristic impedance Zc_(ij) between the transmission lines i and j as an element, Equation (26) may be transformed as follows when k=0 which is a boundary of one of the distributed constant circuit and the lumped constant circuit

[Math. 25]

Uv ₀ ^(m+1) −Zc _(d) ·Iv ₀ ^(m+1) =Uv ₀ ^(m) +Zc _(d)·(Iv ₀ ^(m)−2Iv _(1/2) ^(m+1/2))   (28)

in addition, at k=N which is the other boundary, Equation (26) may be transformed as follows

[Math. 26]

−Uv _(N) ^(m+1) −Zc _(d) ·Iv _(N) ^(m+1) =−Uv _(N) ^(m) +Zc _(d)·(Iv _(N) ^(m)−2Iv _(N−1/2) ^(m+1/2))   (29)

and Equations (28) and (29) after the transformation may be solved using the following discretized boundary condition formulas for k=0 and N corresponding to Equations (24) and (25),

[Math. 27]

(U _(i) ^(m+1) −U _(j) ^(m+1))−Z _(ij) ·I _(ij) ^(m+1)=−γ_(ij)(U _(i) ^(m) −U _(j) ^(m))+δ_(ij) ·Z _(ij) ·I _(ij) ^(m) +V _(ij) ^(m+1) +V _(ij) ^(m)    (30)

[Math. 28]

β·I _(j) ^(m+1)+Σ_(j(≠i)) I _(ij) ^(m+1)=0   (31)

(when Z_(ij)=R_(ij), γ_(ij)=1 and δ_(ij)=1, when Z_(ij)=2L_(ij)/Δt, γ_(ij)=1 and δ_(ij)=−1, and when Z_(ij)=Δt/2C_(ij), γ_(ij)=−1 and δ_(ij)=1, and β is 1 when k=0 and −1 when k=N).

(5) When a connection matrix indicating the presence or absence of involvement in each node connection and the presence or absence of connection with each transmission line in each node is A_(d), a vector having the current I_(i) flowing between the respective nodes and the current I_(i) flowing through each transmission line as an element is vI, a matrix having elements of the impedance Z_(ij) between the respective nodes and the characteristic impedance Zc_(ij) between the transmission lines Z_(d), diagonal matrices with γ_(ij) and γ_(ij) as elements corresponding to a type of elements connected between the nodes are γ_(d) and δ_(d), and a vector having the voltage V_(ij) applied between the nodes as an element is V_(v), Equations (28), (30), and (31) are expressed in a form of a matrix:

     [Math.  29] $\begin{matrix} {{\begin{pmatrix} A_{d}^{T} & {- Z_{d}} \\ 0 & A_{d} \end{pmatrix}\begin{pmatrix} {Uv}_{0}^{m + 1} \\ {vI}_{0}^{m + 1} \end{pmatrix}} = {{{- \begin{pmatrix} {\gamma_{d} \cdot A_{d}^{T}} & {{- \delta_{d}} \cdot Z_{d}} \\ 0 & 0 \end{pmatrix}}\begin{pmatrix} {Uv}_{0}^{m} \\ {{vI}_{0}^{m} - {2{vI}_{1\text{/}2}^{m + {1\text{/}2}}}} \end{pmatrix}} + \begin{pmatrix} {{Vv}^{m + 1} + {Vv}^{m}} \\ 0 \end{pmatrix}}} & (32) \end{matrix}$

Equations (29), (30), and (31) are expressed in a form of a matrix:

     [Math.  30] $\begin{matrix} {{\begin{pmatrix} A_{d}^{T} & {- Z_{d}} \\ 0 & A_{d} \end{pmatrix}\begin{pmatrix} {Uv}_{N}^{m + 1} \\ {vI}_{N}^{m + 1} \end{pmatrix}} = {{{- \begin{pmatrix} {\gamma_{d} \cdot A_{d}^{T}} & {{- \delta_{d}} \cdot Z_{d}} \\ 0 & 0 \end{pmatrix}}\begin{pmatrix} {Uv}_{N}^{m} \\ {{vI}_{N}^{m} - {2{vI}_{N - {1\text{/}2}}^{m + {1\text{/}2}}}} \end{pmatrix}} + \begin{pmatrix} {{Vv}^{m + 1} + {Vv}^{m}} \\ 0 \end{pmatrix}}} & (33) \end{matrix}$

and each equation may be solved.

(6) When considering the insertion of a current source between nodes i and j, Equation (31) is

[Math.  31] $\begin{matrix} {{\left( {A_{d}\mspace{14mu} A_{dJ}} \right)\begin{pmatrix} {vI}_{0}^{m + 1} \\ {vI}_{J_{0}}^{m + 1} \end{pmatrix}} = 0} & (34) \end{matrix}$

(A_(d) is a connection matrix indicating the presence or absence of involvement in each node connection not including a current source and the presence or absence of connection with each transmission line in each node, A_(dJ) is a connection matrix indicating the presence or absence of involvement in each node connection including the current source at each node, vI₀ ^(m+1) is a vector whose elements are a current I_(ij0) ^(m+1) flowing between the respective nodes to which no current source is connected and a current I_(i0) ^(m+1) flowing through each transmission line, and vI_(J0) ^(m+1) is a vector whose elements are a current I_(Jij0) ^(m+1) flowing between the nodes to which the current source is connected) is used, and Equations (28), (30), and (34) is expressed in a form of a matrix

$\begin{matrix} {\mspace{79mu} \left\lbrack {{Math}.\mspace{14mu} 32} \right\rbrack} & \; \\ {{\begin{pmatrix} A_{d}^{T} & {- Z_{d}} \\ 0 & A_{d} \end{pmatrix}\begin{pmatrix} {Uv}_{0}^{m + 1} \\ {vI}_{0}^{m + 1} \end{pmatrix}} = {{{- \begin{pmatrix} {\gamma_{d} \cdot A_{d}^{T}} & {{- \delta_{a}} \cdot Z_{a}} \\ 0 & 0 \end{pmatrix}}\begin{pmatrix} {Uv}_{0}^{m} \\ {{vI}_{0}^{m} - {2{vI}_{1/2}^{m + {1/2}}}} \end{pmatrix}} + \begin{pmatrix} {{Vv}^{m + 1} + {Vv}^{m}} \\ {{- A_{dJ}} \cdot {vI}_{I_{0}}^{m + 1}} \end{pmatrix}}} & (35) \end{matrix}$

Equations (29), (30), and (34) are expressed in a form of a matrix:

$\begin{matrix} {\mspace{79mu} \left\lbrack {{Math}.\mspace{14mu} 33} \right\rbrack} & \; \\ {{\begin{pmatrix} A_{d}^{T} & {- Z_{d}} \\ 0 & A_{d} \end{pmatrix}\begin{pmatrix} {Uv}_{N}^{m + 1} \\ {vI}_{N}^{m + 1} \end{pmatrix}} = {{{- \begin{pmatrix} {\gamma_{d} \cdot A_{d}^{T}} & {{- \delta_{d}} \cdot Z_{d}} \\ 0 & 0 \end{pmatrix}}\begin{pmatrix} {Uv}_{N}^{m} \\ {{vI}_{N}^{m} - {2{vI}_{N - {1/2}}^{m + {1/2}}}} \end{pmatrix}} + \begin{pmatrix} {{Vv}^{m + 1} + {Vv}^{m}} \\ {{- A_{dJ}} \cdot {vI}_{I_{N}}^{m + 1}} \end{pmatrix}}} & (36) \end{matrix}$

and each equation may be solved.

(7) In the value of the antenna term ˜U and ˜A, when a total charge of all the transmission lines at the position x =k·Δx and the time t=m·Δt on the transmission line is Qt_(k) ^(m) and a total current is It_(k) ^(m), a value of Qt_(k) ^(m+1) is calculated by

$\begin{matrix} \left\lbrack {{Math}.\mspace{14mu} 34} \right\rbrack & \; \\ {{\frac{{Qt}_{k}^{m + 1} - {Qt}_{k}^{m}}{\Delta \; t} + \frac{{It}_{k + {1/2}}^{m + {1/2}} - {It}_{k - {1/2}}^{m + {1/2}}}{\Delta \; x}} = 0} & (37) \end{matrix}$

and the values of the antenna terms ˜U and ˜A may be calculated by the followings Equations.

$\begin{matrix} {\mspace{79mu} \left\lbrack {{Math}.\mspace{14mu} 35} \right\rbrack} & \; \\ {{{}_{}^{}{}_{}^{m + 1}} = {\frac{1}{4\; \pi \; ɛ}\left\lbrack {{\sum\limits_{k^{\prime} = 0}^{k}\; \frac{{Qt}_{k^{\prime}}^{m + 1 - {({k - k^{\prime}})}} - {Qt}_{k}^{m + 1}}{k - k^{\prime}}} + {\sum\limits_{k^{\prime} = k}^{N}\; \frac{{Qt}_{k^{\prime}}^{m + 1 + {({k - k^{\prime}})}} - {Qt}_{k}^{m + 1}}{- \left( {k - k^{\prime}} \right)}}} \right\rbrack}} & (38) \\ {\mspace{79mu} \left\lbrack {{Math}.\mspace{14mu} 36} \right\rbrack} & \; \\ {{{}_{}^{}{}_{k + {1/2}}^{m + {1/2}}} = {\frac{\mu}{4\; \pi}\left\lbrack {{\sum\limits_{k^{\prime} = 0}^{k}\; \frac{{It}_{k^{\prime} + {1/2}}^{m + {1/2} - {({k - k^{\prime}})}} - {It}_{k + {1/2}}^{m + {1/2}}}{k - k^{\prime}}} + {\sum\limits_{k^{\prime} = k}^{N}\; \frac{{It}_{k^{\prime} + {1/2}}^{m + {1/2} + {({k - k^{\prime}})}} - {It}_{k + {1/2}}^{m + {1/2}}}{- \left( {k - k^{\prime}} \right)}}} \right\rbrack}} & (39) \end{matrix}$

(8) The calculating step may repeatedly perform: in m=0, a first calculating sub-step of calculating Uv₀ ¹ and vI₀ ¹ by Equation (35); a second calculating sub-step of calculating Qt₀ ¹ by Equation (37); a third calculating sub-step of calculating ˜U₀ ¹ by Equation (38); a fourth calculating sub-step of calculating Qt_(k) ¹ (k=1, 2, . . . , N−1) by Equation (37); a fifth calculating sub-step of calculating ˜U_(k) ¹ (k=1, 2, . . . , N−1) by Equation (38); a sixth calculating sub-step of calculating Uv_(k) ¹ (k=1, 2, . . . , N−1) by Equation (26); a seventh calculating sub-step of calculating Uv_(N) ¹ and vI_(N) ¹ by Equation (36); an eighth sub-step of calculating Qt_(N) ¹ by Equation (37); a ninth calculating sub-step of calculating ˜U_(N) ¹ by Equation (38); a tenth calculating sub-step of calculating ˜A_(k+1/2) ^(1/2) (k=0, 1, . . . , N−1) by equation (39); and an eleventh calculating sub-step of calculating Iv_(k+1/2) ^(3/2) (k=0, 1, . . . , N−1) by Equation (27), and in m≥1, an twelfth calculating sub-step of calculating Uv₀ ^(m+1) and vI₀ ^(m+1) by Equation (35); a thirteenth sub-step of calculating Qt₀ ^(m+1) by Equation (37); a fourteenth calculating sub-step of calculating ˜U₀ ^(m+1) (k=1, 2, . . . , N−1) by Equation (38); a fifteenth sub-step of calculating Qt_(k) ^(m+1) (k=1, 2, . . . , N−1) by Equation (37); a sixteenth calculating sub-step of calculating ˜U_(k) ^(m+1) (k=1, 2, . . . , N−1) by Equation (38); a seventeenth calculating sub-step of calculating Uv_(k) ^(m+1) (k=1, 2, . . . , N−1) by Equation (26); an eighteenth calculating sub-step of calculating Uv_(N) ^(m+1) and vI_(N) ^(m+1) by Equation (36); a nineteenth calculating sub-step of calculating Qt_(N) ^(m+1) by Equation (37); a twentieth calculating sub-step of calculating ˜U_(N) ^(m+1) by Equation (38); a twenty-first calculating sub-step of calculating ˜A_(k+1/2) ^(m+1/2) (k=0, 1, . . . , N−1) by Equation (39); and a twenty-second calculating sub-step of calculating Iv_(k+1/2) ^(1+3/2) (k=0, 1, 2, . . . , N−1) by Equation (27) until a value of m reaches a predetermined value while incrementing m by 1.

Therefore, it is possible to comprehensively calculate the potential and current in the multi-conductor transmission line constituting the distributed constant circuit, the potential and the current in the element constituting the lumped constant circuit connected to the multi-conductor transmission line, and the electromagnetic fields including noise generated from each circuit, without performing a complicated calculation.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a diagram illustrating an example of a circuit configuration to which a calculation method of the present invention is applied.

FIG. 2 is a diagram illustrating an example of a calculation flow of a calculation method of the present invention.

DESCRIPTION OF EMBODIMENTS

<Boundary Condition>

It is a basic equation of a new transmission theory described as the background art.

$\begin{matrix} \left\lbrack {{Math}.\mspace{14mu} 37} \right\rbrack & \; \\ {\frac{\partial{U_{i}\left( {t,x} \right)}}{\partial t} = {{- {\sum\limits_{j = 1}^{n}\; {P_{ij} \cdot \frac{\partial{I_{j}\left( {t,x} \right)}}{\partial x}}}} + \frac{\partial{{\,^{\sim}U}\left( {t,x} \right)}}{\partial t}}} & (16) \\ \left\lbrack {{Math}.\mspace{14mu} 38} \right\rbrack & \; \\ {\frac{\partial{U_{i}\left( {t,x} \right)}}{\partial x} = {{- {\sum\limits_{j = 1}^{n}\; {L_{ij} \cdot \frac{\partial{I_{j}\left( {t,x} \right)}}{\partial t}}}} - \frac{\partial{{\,^{\sim}A}\left( {t,x} \right)}}{\partial t} - {R_{i} \cdot {I_{i}\left( {t,x} \right)}}}} & (17) \\ \left\lbrack {{Math}.\mspace{14mu} 39} \right\rbrack & \; \\ {{{\,^{\sim}U}\left( {t,x} \right)} = {\frac{1}{4\; \pi \; ɛ}{\int_{0}^{w}{{dx}^{\prime}\frac{{Q_{t}\left( {{t - {\sqrt{{x - x^{\prime}}}/c}},x^{\prime}} \right)} - {Q_{t}\left( {t,x} \right)}}{{x - x^{\prime}}}}}}} & (11) \\ \left\lbrack {{Math}.\mspace{14mu} 40} \right\rbrack & \; \\ {{{\,^{\sim}A}\left( {t,x} \right)} = {\frac{\mu}{4\; \pi}{\int_{0}^{w}{{dx}^{\prime}\frac{{I_{t}\left( {{t - {\sqrt{{x - x^{\prime}}}/c}},x^{\prime}} \right)} - {I_{t}\left( {t,x} \right)}}{{x - x^{\prime}}}}}}} & (12) \end{matrix}$

In order to solve these equations, it is necessary to provide an appropriate boundary condition between a transmission line which is a distributed constant circuit and a power supply or load which is a lumped constant circuit, FIG. 1 shows a configuration example of an electric circuit in which a power supply V_(ij)(t) and a resistor r_(ij) are connected to one end (power supply side) of an n-conductor transmission line and a resistor R_(ij) is connected to the other end (load side). Here, t is the time, subscripts i and j are the numbers of the transmission line and the node, the transmission line i is connected to the node i of the same subscript, and is a transmission line and node different from i. ij is the number indicating between the transmission lines i and j and between the nodes i and j. In FIG. 1, as a specific example, in a three-conductor transmission line, at the power supply side boundary (x=0) which is one end of each transmission line, a power supply V₁₂ and a resistor r₁₂ are connected between the transmission lines 1 and 2 (between the nodes 1 and 2), and a resistor r₂₃ is connected between the transmission lines 2 and 3 (between the nodes 2 and 3). On the load side boundary (x=w (w is the transmission line length)) which is the other end of each transmission line, R₁₂ is connected between the transmission line 1 (node 1) and the node 4, R₄₂ is connected between the node 4 and the transmission line 2 (node 2), R₂₃ is connected between the transmission lines 2 and 3 (between the nodes 2 and 3), H₄₅ is connected between the node 4 and the node 5, and R₅₃ is connected between the node 5 and the transmission line 3 (node 3). In addition, U_(i)(t, x) and I_(i)(t, x) are the scalar potential (potential) and current at the time t and the position x on the transmission line i, respectively. Note that the scalar potential (potential) corresponds to the potential of the node of the lumped constant circuit at the boundary (x=0 and x=w)

Under such a circuit configuration, the following boundary condition formula can be obtained from the Ohm' s law at the power supply side boundary.

U _(i)(t,x=0)−U _(j)(t,x=0)=V _(ij)(t)+r _(ij) ·I _(ij)(t)   (40)

In addition, in the connection node i between the transmission line i and the power supply or the like, the following boundary condition formula can be further obtained from the law of current conservation.

I _(i)(t,x=0)+Σ_(j(≠i)) I _(ij)(t)=0   (41)

Note that Equation (41) assumes that the current flows in the direction indicated by the arrow in FIG. 1 and is established under the definition that the direction flowing out from the connection node is a positive direction and the direction flowing into the connection node is a negative direction. In the following, in order to match the current calculation of the whole circuit, the definition of the direction of the current in the current calculation formula is the same as this.

On the other hand, the next boundary condition formula can be obtained from the Ohm' s law even at the load side boundary.

U _(i)(t,x=w)−U _(j)(t,x=w)=V _(ij)(t)+R _(ij) ·i _(ij)(t)   (42)

Equation (42) also includes a power supply term similarly to Equation (40) on the power supply side. This is because it is assumed that the power supply is inserted V_(ij) (t)=0 in the case of the example of FIG. 1 in which the power supply is not inserted.

In addition, the following boundary condition formula can be obtained from the law of current conservation even at the connection node i between the transmission line i and the load.

−I _(i)(t,x=w)+Σ_(j(≠i)) I _(ij)(t)=0   (43)

The sign of Equation (41) on the power supply side is different from the sign of because the current flows out from the power supply side connection node, whereas the current flows into the load side connection node.

In FIG. 1, a case where the resistor R_(ij) is connected as a load is exemplified. However, when the inductor L_(ij) and the capacitor C_(ij) are connected, Equation (42) has the following form.

$\begin{matrix} \left\lbrack {{Math}.\mspace{14mu} 41} \right\rbrack & \; \\ {{{U_{i}\left( {t,x} \right)} - {U_{j}\left( {t,x} \right)}} = {{V_{ij}(t)} + {L_{ij}\frac{d}{dt}{I_{ij}(t)}}}} & (44) \\ \left\lbrack {{Math}.\mspace{14mu} 42} \right\rbrack & \; \\ {{\frac{d}{dt}\left( {{U_{i}\left( {t,x} \right)} - {U_{j}\left( {t,x} \right)}} \right)} = {{\frac{d}{dt}{V_{ij}(t)}} + {C_{ij}^{- 1} \cdot {I_{ij}(t)}}}} & (45) \end{matrix}$

Then, Equations (92), (44), and (45) can be generalized as follows.

U _(i)(t,x)−U _(j)(t,x)=V _(ij)(t)+Z _(ij) ·Δ·I _(ij)(t)   (46)

In Equation (46), Δ is 1 when Z_(ij)=R_(ij), d/dt when Z_(ij)=L_(ij), and (d/dt)⁻¹when Z_(ij)=1/C_(ij).

In this way, by giving the boundary conditions to the basic equations of the new transmission theory, it is possible to comprehensively calculate the potential and current of the transmission line in the electric circuit, the potential and current of the element, and the electromagnetic field including noise generated from the electric circuit.

<Application of FDTD Method>

The calculation of the basic equations (16) and (17) of the new transmission theory can be performed efficiently by using a Finite Difference Time Domain (FDTD) method. In the FDTD method analysis is performed by a structure called a Yee grid that shifts the grid where the unknown electric field is arranged and the grid where the unknown magnetic field is arranged by half the width of the grid. In the FDTD method, the Maxwell's equation (Faraday's electromagnetic induction law and Ampere's law) is spatially and temporally differentiated by relational expressions working between these unknown electric and magnetic fields and adjacent unknown electric field and magnetic field (discretization), and based on this, the unknown electric field and the magnetic field are updated in units of certain time steps to obtain the whole electromagnetic field behavior. According to this analysis method, the electric field and the magnetic field can be obtained alternately by updating the electric field at a certain time step, updating the magnetic field after 1/2 time step, and updating the electric field after one time step. In particular, by setting the interval of the grid used for discretizing the space and time to be sufficiently small, it is possible to simulate the temporal change of the electromagnetic field in detail and efficiently. In the present invention, this technique is used for obtaining the potential and the current in the transmission line. In the boundary condition between the transmission line part and the lumped circuit part, the calculation is possible by using the result calculated by FDTD and the theory based on the circuit theory used on lumped constant side. Specifically, on the lumped constant side, Kirchhoff's voltage law, Kirchhoff s current law, and the voltage-current characteristics of the element can be used.

First, it is necessary to discretize the basic equations (16) and (17) of the new transmission theory when performing the calculation by using the FDTD method. At this time, at the position x=k·Δx (k=0, 1, . . . , N, w=N·Δx) on the transmission line i and the time t=m·Δt (m=0, 1, . . . arbitrary), the scalar potential is expressed as U_(k) ^(m) and the current is expressed as I_(k) ^(m). In a case where the part of k is k+1/2 and the part of m is m+1/2, it is expressed as I_(k+1/2) ^(m+1/2). In this way, the grid of the FDTD method is defined in a range from 0 to the transmission line length w in the x direction and in a range up to an arbitrary time in the t direction. At this time, Equations (16) and (17) can be discretized as shown in, for example, Equations (47) and (48).

$\begin{matrix} {\mspace{79mu} \left\lbrack {{Math}.\mspace{14mu} 43} \right\rbrack} & \; \\ {\mspace{79mu} {\frac{{Uv}_{k}^{m + 1} - {Uv}_{k}^{m}}{\Delta \; t} = {{{- P_{d}}\frac{{Iv}_{k + {1/2}}^{m + {1/2}} - {Iv}_{k - {1/2}}^{m + {1/2}}}{\Delta \; x}} + \frac{{{}_{}^{}{}_{}^{m + 1}} - {{}_{}^{}{}_{}^{}}}{\Delta \; t}}}} & (47) \\ {\mspace{79mu} \left\lbrack {{Math}.\mspace{14mu} 44} \right\rbrack} & \; \\ {\frac{{Uv}_{k + 1}^{m + 1} - {Uv}_{k}^{m + 1}}{\Delta \; x} = {{{- L_{d}}\frac{{Iv}_{k + {1/2}}^{m + {3/2}} - {Iv}_{k + {1/2}}^{m + {1/2}}}{\Delta \; t}} - \frac{{{}_{}^{}{}_{k + {1/2}}^{m + {1/2}}} - {{}_{}^{}{}_{k + {1/2}}^{m - {1/2}}}}{\Delta \; t} - {R_{d}\frac{{Iv}_{k + {1/2}}^{m + {3/2}} - {Iv}_{k + {1/2}}^{m + {1/2}}}{2}}}} & (48) \end{matrix}$

Here, Uv_(k) ^(m) is a vector with U_(k) ^(m) as the element for each transmission line i, Iv_(k) ^(m) is a vector with I_(k) ^(m) as the element for each transmission line i, P_(d) is a matrix with P_(ij) as its element, L_(d) is a matrix with L_(ij) as its element, and R_(d) is a matrix with R_(i) as a diagonal element.

<Boundary Condition in Case of FDTD Method>

Next, the discretized basic equations are solved by giving the boundary conditions. Since the effect of the antenna is generated on the transmission line and is not generated at the boundary portion which is the end of the transmission line, it is possible to solve the equation with the antenna term removed from the basic equation. The following is obtained by simply substituting k=0 indicating the boundary position of one of the distributed constant circuit and the lumped constant circuit to the equation obtained by removing the antenna term ˜U from Equation (47).

$\begin{matrix} \left\lbrack {{Math}.\mspace{14mu} 45} \right\rbrack & \; \\ {\frac{{Uv}_{0}^{m + 1} - {Uv}_{0}^{m}}{\Delta \; t} = {{- P_{d}}\frac{{Iv}_{1/2}^{m + {1/2}} - {Iv}_{{- 1}/2}^{m + {1/2}}}{\Delta \; x}}} & (49) \end{matrix}$

At this time, since the term of Iv_(−1/2) ^(m+1/2) becomes x<0 and falls outside the definition range of the grid, it is transformed as follows so that it falls within the definition range and the error becomes small.

$\begin{matrix} \left\lbrack {{Math}.\mspace{14mu} 46} \right\rbrack & \; \\ {\frac{{Uv}_{0}^{m + 1} - {Uv}_{0}^{m}}{\Delta \; t} = {{- P_{d}}\frac{{Iv}_{1/2}^{m + {1/2}} - {\frac{1}{2}\left( {{Iv}_{0}^{m + 1} + {Iv}_{0}^{m}} \right)}}{\Delta \; {x/2}}}} & (50) \end{matrix}$

Such a transformation is similarly performed when Qt₀ ¹ is determined. Furthermore, when the signal is transmitted at the speed of light c on the transmission line and Zc_(d) is a matrix having the characteristic impedance Zc_(ij) between the transmission lines i and j as an element, Zc_(ij)=P_(ij)/c and c·Δt=Δx, and thus Equation (50) can be transformed as follows.

[Math. 47]

Uv ₀ ^(m+1) −Zc _(d) ·Iv ₀ ^(m+1) =Uv ₀ ^(m) +Zc _(d)·(Iv ₀ ^(m)−2Iv _(1/2) ^(m+1/2))   (51)

In addition, the following is obtained by simply substituting k=N indicating the boundary position of the other of the distributed constant circuit and the lumped constant circuit to the equation obtained by removing the antenna term ˜U from Equation (47).

$\begin{matrix} \left\lbrack {{Math}.\mspace{14mu} 48} \right\rbrack & \; \\ {\frac{{Uv}_{N}^{m + 1} - {Uv}_{N}^{m}}{\Delta \; t} = {{- P_{d}}\frac{{Iv}_{N + {1/2}}^{m + {1/2}} - {Iv}_{N - {1/2}}^{m + {1/2}}}{\Delta \; x}}} & (52) \end{matrix}$

At this time, since the term of Iv_(N+1/2) ^(m+1/2) becomes x>w and falls outside the definition range of the grid, it is transformed as follows so that it falls within the definition range and the error becomes small.

$\begin{matrix} \left\lbrack {{Math}.\mspace{14mu} 49} \right\rbrack & \; \\ {\frac{{Uv}_{N}^{m + 1} - {Uv}_{N}^{m}}{\Delta \; t} = {{- P_{d}}\frac{{\frac{1}{2}\left( {{Iv}_{N}^{m + 1} + {Iv}_{N}^{m}} \right)} - {Iv}_{N - {1/2}}^{m + {1/2}}}{\Delta \; {x/2}}}} & (53) \end{matrix}$

Such a transformation is similarly performed when Qt_(N) ¹ is determined. Furthermore, Equation (53) can be transformed as follows.

[Math. 50]

−Uv _(N) ^(m+1) −Zc _(d) ·Iv _(N) ^(m+1) =−Uv _(N) ^(m) +Zc _(d)·(Iv _(N) ^(m)−2Iv _(N−1/2) ^(m+1/2))   (54)

The reason why Equation (51) in the case of k=0 and the sign of the first term on both sides are different is because when the direction of the current is k=0, the current flows out from the connection node toward the transmission line, and in the case of k=N, current is defined to flow from the transmission line to the connection node.

The boundary conditions are given to the discretized basic equations (51) and (54) in this way. When the resistor R_(ij), the inductor L_(ij) or the capacitor C_(ij) is connected between the transmission lines i and j and the current flowing therethrough is I_(ij)(t), the following boundary condition formula is obtained from Ohm' s law. Note that a case where the power supply V_(ij)(t) is connected between the transmission lines i and j together with these loads will be omitted herein for simplicity of the equation.

$\begin{matrix} {{{U_{i}\left( {t,x} \right)} - {U_{i}\left( {t,x} \right)}} = {R_{ij} \cdot {I_{ij}(t)}}} & (55) \\ \left\lbrack {{Math}.\mspace{14mu} 51} \right\rbrack & \; \\ {{{U_{i}\left( {t,x} \right)} - {U_{i}\left( {t,x} \right)}} = {L_{ij}\frac{d}{dt}{I_{ij}(t)}}} & (56) \\ \left\lbrack {{Math}.\mspace{14mu} 52} \right\rbrack & \; \\ {{\frac{d}{dt}\left( {{U_{i}\left( {t,x} \right)} - {U_{j}\left( {t,x} \right)}} \right)} = {C_{ij}^{- 1} \cdot {I_{ij}(t)}}} & (57) \end{matrix}$

When these equations are discretized, they become as follows.

$\begin{matrix} \left\lbrack {{Math}.\mspace{14mu} 53} \right\rbrack & \; \\ {\frac{\left( {U_{i}^{m + 1} - U_{j}^{m + 1}} \right) + \left( {U_{i}^{m} - U_{j}^{m}} \right)}{2} = {R_{ij}\frac{I_{ij}^{m + 1} + I_{ij}^{m}}{2}}} & (58) \\ \left\lbrack {{Math}.\mspace{14mu} 54} \right\rbrack & \; \\ {\frac{\left( {U_{i}^{m + 1} - U_{j}^{m + 1}} \right) + \left( {U_{i}^{m} - U_{j}^{m}} \right)}{2} = {L_{ij}\frac{I_{ij}^{m + 1} + I_{ij}^{m}}{2}}} & (59) \\ \left\lbrack {{Math}.\mspace{14mu} 55} \right\rbrack & \; \\ {\frac{\left( {U_{i}^{m + 1} - U_{j}^{m + 1}} \right) + \left( {U_{i}^{m} - U_{j}^{m}} \right)}{\Delta \; t} = {\frac{1}{C_{ij}}\frac{I_{ij}^{m + 1} + I_{ij}^{m}}{2}}} & (60) \end{matrix}$

Then, Equations (58) to (60) can be generalized as follows,

[Math. 56]

(U _(i) ^(m+1) −U _(j) ^(m+1))−Z _(ij) ·I _(ij) ^(m+1)=−γ_(ij)(U _(i) ^(m) −U _(j) ^(m))+δ_(ij) ·Z _(ij) ·I _(ij) ^(m)   (61)

Here, when Z_(ij)=R_(ij), γ_(ij)=1 and δ_(ij)=1, when Z_(ij)=2L_(ij)/Δt, γ_(ij)=1 and δ_(ij)=−1, and when Z_(ij)=Δt/2C_(ij), γ_(ij)=−1 and δ_(ij)=1.

When the power supply V_(ij) is further connected between the transmission lines i and j, the following equation may be applied in consideration of discretized V_(ij) in Equation (61).

[Math. 57]

(U _(i) ^(m+1) −U _(j) ^(m+1))−Z _(ij) ·I _(ij) ^(m+1)=−γ_(ij)(U _(i) ^(m) −U _(j) ^(m))+δ_(ij) ·Z _(ij) ·I _(ij) ^(m) +V _(ij) ^(m+1) +V _(ij) ^(m)    (62)

In addition, as the boundary condition formula, the following relational expression is obtained at the connection node i between the transmission line i and the power supply or load from the law of current conservation.

[Math. 58]

β·I _(j) ^(m+1)+Σ_(j(≠i)) I _(ij) ^(m+1)=0   (63)

Here, when k=0, β=1 since the direction of the current is a direction of flowing out from the connection node, and when k=N, β=−1 since the direction of the current is a direction of flowing into the connection node.

Note that the method of setting the boundary condition as described above can be similarly applied to a case where the element is a mutual inductor or a cascade power supply.

<Calculation at Boundary Condition (k=0)>

The value of the scalar potential U and the current I at the boundary condition of k=0 can be obtained by solving the simultaneous equations of Equations (51), (62), and (63). Equations (51), (62), and (63) can be collectively represented in the form of, for example, the following matrix.

$\begin{matrix} {\mspace{79mu} \left\lbrack {{Math}.\mspace{14mu} 59} \right\rbrack} & \; \\ {{\begin{pmatrix} A_{d}^{T} & {- Z_{d}} \\ 0 & A_{d} \end{pmatrix}\begin{pmatrix} {Uv}_{0}^{m + 1} \\ {vI}_{0}^{m + 1} \end{pmatrix}} = {{{- \begin{pmatrix} {\gamma_{d} \cdot A_{d}^{T}} & {{- \delta_{d}} \cdot Z_{d}} \\ 0 & 0 \end{pmatrix}}\begin{pmatrix} {Uv}_{0}^{m} \\ {{vI}_{0}^{m} - {2{vI}_{1/2}^{m + {1/2}}}} \end{pmatrix}} + \begin{pmatrix} {{Vv}^{m + 1} + {Vv}^{m}} \\ 0 \end{pmatrix}}} & (64) \end{matrix}$

A_(d) in Equation (64) is a connection matrix indicating the presence or absence of involvement in each node connection at each node and the presence or absence of connection with each transmission line. For example, in the configuration of FIG. 1, three nodes (1 to 3) indicated by solid circles can be conceived on the power supply side where k=0 (x=0). These are regarded as the row direction, and the presence or absence of involvement with the inter-node connection (in this case, between the nodes 12 and 23) and the presence or absence of connection with the three transmission lines (1 to 3) are expressed in the column direction as follows.

$\begin{matrix} \left\lbrack {{Math}.\mspace{14mu} 60} \right\rbrack & \; \\ {A_{d} = \begin{pmatrix} 1 & 0 & 1 & 0 & 0 \\ {- 1} & 1 & 0 & 1 & 0 \\ 0 & {- 1} & 0 & 0 & 1 \end{pmatrix}} & (65) \end{matrix}$

That is, in this case, since the node 1 relates to the connection between the nodes 12 and is connected to the transmission line 1 and the current is defined to flow out respectively, 1 is allocated to the first and third columns respectively. On the other hand, since there is no connection to the connection between the nodes 23 and the connection with the transmission lines 2 and 3, 0 is arranged in the second, fourth, and fifth columns. In addition, since the node 2 relates to the connection between the nodes 12 and 23 and is connected to the transmission line 2 and defined from the direction of the current flowing from the node 1, −1 is arranged in the first column. Since it is defined as the direction in which the current flows out to the node 3 and the transmission line 2, 1 is arranged in the second and fourth columns. On the other hand, since there is no connection with the transmission lines 1 and 3, 0 is arranged in the third and fifth columns Further, since the node 3 relates to the connection between the nodes 23 and is connected to the transmission line 3 and the node 3 is defined the direct on in which the current flows from the node 2, −1 is arranged in the second column. Since it is defined as the direct on in which the current, flows out to the transmission line 3, 1 is arranged in the fifth column. On the other hand, since there is no connection to the connection between the nodes 12 and connection with the transmission lines 1 and 2, 0 is allocated to the first, third, and fourth columns. By constructing the matrix in this manner, for example, when the description of k=0 is omitted and the calculation of A_(d) ^(T)·Uv^(m+1) on the left side of Equation (64) is described,

$\begin{matrix} \left\lbrack {{Math}.\mspace{14mu} 61} \right\rbrack & \; \\ {{A_{d}^{T} \cdot {Uv}^{m + 1}} = {{\begin{pmatrix} 1 & {- 1} & 0 \\ 0 & 1 & {- 1} \\ 1 & 0 & 0 \\ 0 & 1 & 0 \\ 0 & 0 & 1 \end{pmatrix}\begin{pmatrix} U_{1}^{m + 1} \\ U_{2}^{m + 1} \\ U_{3}^{m + 1} \end{pmatrix}} = \begin{pmatrix} {U_{1}^{m + 1} - U_{2}^{m + 1}} \\ {U_{2}^{m + 1} - U_{3}^{m + 1}} \\ U_{1}^{m + 1} \\ U_{2}^{m + 1} \\ U_{3}^{m + 1} \end{pmatrix}}} & (66) \end{matrix}$

(U_(i) ^(m+l)−U_(j) ^(m+1)) in the first term on the left side of Equation (62) in the first and second rows, and Uv^(m+1) in the first term of the left side of Equation (51) in the third to fifth rows are expressed respectively.

Z_(d) in Equation (64) is a matrix with the impedance Z_(ij) between the nodes and the characteristic impedance Zc_(ij) between the transmission lines as elements. For example, in the configuration of FIG. 1, r₁₂ is connected between the nodes 1 and 2 on the power supply side where k=0 (x=0), r₂₃ is connected between the nodes 2 and 3, and there are three transmission lines, and thus, Z_(d) is expressed as follows.

$\begin{matrix} \left\lbrack {{Math}.\mspace{14mu} 62} \right\rbrack & \; \\ {Z_{d} = \begin{pmatrix} r_{12} & 0 & 0 & 0 & 0 \\ 0 & r_{23} & 0 & 0 & 0 \\ 0 & 0 & {Zc}_{11} & {Zc}_{12} & {Zc}_{13} \\ 0 & 0 & {Zc}_{21} & {Zc}_{22} & {Zc}_{23} \\ 0 & 0 & {Zc}_{31} & {Zc}_{32} & {Zc}_{33} \end{pmatrix}} & (67) \end{matrix}$

vI₀ ^(m+1) in Equation (64) is a vector having the current I_(ij) flowing between the respective nodes and the current I_(i) flowing through the respective transmission lines as elements. For example, in the configuration of FIG. 1, I₁₂ ₀ ^(m+1) flows between the nodes 1 and 2 on the power supply side where k=0 (x=0), I₂₃ ₀ ^(m+1) flows between the nodes 2 and 3, and there are three transmission lines, and thus vI₀ ^(m+1) is expressed as follows.

[Math. 63]

vI ₀ ^(m+1)=(I ₁₂ ₀ ^(m+1) I ₂₃ ₀ ^(m+1) I ₁ ₀ ^(m+1) I ₂ ₀ ^(m+1) I ₃ ₀ ^(m+1))^(T)   (68)

By constituting Z_(d) and vI₀ ^(m+1) in this way, the calculation result of Z_(d)·vI₀ ^(m+1) on the left side of Equation (64) is a vector in which Z_(ij)·I_(ij) ^(m+1) in the second term on the left side of Equation (62) are elements in the first and second rows, and Zc_(d)·Iv₀ ^(m+1) of the second term on the left side of Equation (51) are elements in the third to fifth rows. That is, the matrix and vector to which A_(d) ^(T) or Z_(d)are applied are expressed by the elements of Equation (62) related to inter-node connection in the first and second rows, and the elements of Equation (51) related to the transmission line in the third to fifth rows. This also applies to the relationship between the right side of Equation (64) and the right side of Equations (62) and (51).

γ_(d) and δ_(d) in Equation (64) are diagonal matrices with γ_(ij) and δ_(ij) corresponding to the type of elements connected between nodes as elements. For example, in the configuration of FIG. 1, on the power supply side where k=0 (x=0), the resistor r₁₂ is connected between the nodes 1 and 2, and the resistor r₂₃ is connected between the nodes 2 and 3. As described in the description of Equation (61), when Z_(ij)=resistance R_(ij), γ_(ij)=1 and δ_(ij)=1. Therefore, γ_(d) and δ_(d) are expressed as follows.

$\begin{matrix} \left\lbrack {{Math}.\mspace{14mu} 64} \right\rbrack & \; \\ {\gamma_{d} = \begin{pmatrix} 1 & 0 & 0 & 0 & 0 \\ 0 & 1 & 0 & 0 & 0 \\ 0 & 0 & {- 1} & 0 & 0 \\ 0 & 0 & 0 & {- 1} & 0 \\ 0 & 0 & 0 & 0 & {- 1} \end{pmatrix}} & (69) \\ \left\lbrack {{Math}.\mspace{14mu} 65} \right\rbrack & \; \\ {\delta_{d} = \begin{pmatrix} 1 & 0 & 0 & 0 & 0 \\ 0 & 1 & 0 & 0 & 0 \\ 0 & 0 & 1 & 0 & 0 \\ 0 & 0 & 0 & 1 & 0 \\ 0 & 0 & 0 & 0 & 1 \end{pmatrix}} & \left( 70 \right. \end{matrix}$

In the matrix γ_(d), 1 of the first row and the first column and 1 of the second row and the second column are y_(ij)=1 corresponding to r₁₂ and r₂₃, respectively. Similarly, in the matrix δ_(d), 1 of the first row and the first column and 1 of the second row and the second column are δ_(ij)=1 corresponding to r₁₂ and r₂₃ is, respectively. On the other hand, three diagonal elements of the third row and the third column, the fourth row and the fourth column, and the fifth row and the fifth column correspond to transmission lines 1 to 3, respectively. The transmission line itself has the property of a capacitor. Since γ_(ij)=−1 and δ_(ij)=1 when Z_(ij)=capacitor (Δt/2C_(ij)) as described in the description of Equation (61), −1 is assigned to the three diagonal elements of γ_(d), and the three diagonal elements of δ_(d) are 1.

Since vI_(1/2) ^(m+1/2) in Equation (64) is related only to Equation (51), the elements of the first and second rows related to Equation (62) are 0. Therefore, it is expressed as follows.

[Math. 66]

vI _(1/2) ^(m+1/2)=(0 0 I ₁ _(1/2) ^(m+1/2) I ₂ _(1/2) ^(m+1/2) I ₃ _(1/2) ^(m+1/2))^(T)   (71)

On the other hand, since Vv^(m) in Equation (64) relates only to Equation (62), elements in the third to fifth rows related to Equation (51) are zero. Therefore, it is expressed as follows

[Math. 67]

Vv ^(m)=(V ₁₂ ^(m) V ₂₃ ^(m)0 0 0)^(T)   (72)

A_(d)·vI₀ ^(m+1) on the left side of Equation (64) represents the left side of Equation (63), and the right side (=0) corresponding to A_(d)·vI₀ ^(m+1) represents the right side of Equation (63)

In calculating the values of U and I, Equation (64) is transformed as follows, so that the values of U and I at time (m+1)Δt can be obtained from the values of U and I at the preceding time mΔt or (m+1/2)Δt.

$\begin{matrix} {\mspace{79mu} \left\lbrack {{Math}.\mspace{14mu} 68} \right\rbrack} & \; \\ {\begin{pmatrix} {Uv}_{0}^{m + 1} \\ {vI}_{0}^{m + 1} \end{pmatrix} = {{{- \begin{pmatrix} A_{d}^{T} & {- Z_{d}} \\ 0 & A_{d} \end{pmatrix}^{- 1}}\begin{pmatrix} {\gamma_{d} \cdot A_{d}^{T}} & {{- \delta_{d}} \cdot Z_{d}} \\ 0 & 0 \end{pmatrix}\begin{pmatrix} {Uv}_{0}^{m} \\ {{vI}_{0}^{m} - {2\; {vI}_{1/2}^{m + {1/2}}}} \end{pmatrix}} + {\begin{pmatrix} A_{d}^{T} & {- Z_{d}} \\ 0 & A_{d} \end{pmatrix}^{- 1}\begin{pmatrix} {{Vv}^{m + 1} + {Vv}^{m}} \\ 0 \end{pmatrix}}}} & (73) \end{matrix}$

Equation (63) constituting a part of Equation (64) is a conditional expression in a case where the current source is not included in the circuit. In consideration of the presence of the current source, the following transformation is needed.

When assuming that A_(dt) is a connection matrix indicating the presence or absence of connection with other nodes in each node and the presence or absence of connection with each transmission line and vtI₀ ^(m+1) is a vector having the current flowing between nodes and the current, flowing through each transmission line as elements, the following relational expression is established from the Kirchhoff s current law.

A _(dt) ·vtI ₀ ^(m+)=0   (74)

The connection matrix A_(dt) can be divided into a connection matrix A_(d) indicating the presence or absence of involvement in the connection between the nodes not including the current source and the presence or absence of connection with each transmission line, and a connection matrix A_(dJ) indicating the presence or absence of involvement in the connection to the nodes including the current source at each node. For example, when the current source flowing from the node 2 to the node 3 is inserted instead of the resistor r₂₃ between the nodes 2 and 3 on the power supply side in the configuration of FIG. 1, the connection matrix A_(d) and the connection matrix A_(dJ) are expressed as follows.

$\begin{matrix} \left\lbrack {{Math}.\mspace{14mu} 69} \right\rbrack & \; \\ {A_{d} = \begin{pmatrix} 1 & 1 & 0 & 0 \\ {- 1} & 0 & 1 & 0 \\ 0 & 0 & 0 & 1 \end{pmatrix}} & (75) \\ \left\lbrack {{Math}.\mspace{14mu} 70} \right\rbrack & \; \\ {A_{dJ} = \begin{pmatrix} 0 \\ 1 \\ {- 1} \end{pmatrix}} & (76) \end{matrix}$

The connection matrix A_(d) has the nodes 1 to 3 in the row direction, and the column direction indicates the presence or absence of involvement in each node connection (in this case, between the nodes 12) to which the current source is not connected and the presence or absence of connection with the three transmission lines (1 to 3). That is, in this case, since the node 1 relates to the connection between the nodes 12 and is connected to the transmission line 1 and the current is defined to flow out respectively, 1 is allocated to the first and second columns respectively. On the other hand, since there is no connection to the transmission lines 2 and 3, 0 is arranged. In addition, since the node 2 relates to the connection between the nodes 12 and is connected to the transmission line 2 and defined from the direction of the current flowing from the node 1, −1 is arranged. Since it is defined as the direction in which the current flows out to the transmission line 2, 1 is arranged. On the other hand, since there is no connection with the transmission lines 1 and 3, 0 is arranged. Further, since the node 3 is connected to the transmission line 3 and defined in the direction in which the current flows out to the transmission line 3, 1 is arranged, and since there is no connection with the node 1 and the transmission lines 1 and 2, 0 is arranged. The connection matrix A_(dJ) indicates the presence or absence of involvement in each node connection to each node connection (in this case, between the nodes 23) in which the row direction indicates the nodes 1 to 3 and the current source is connected in the column direction. That is, in this case, since node 1 does not relate to the connection between nodes 23, 0 is arranged to the row of the node 1, and since the nodes 2 and 3 relate to the connection between the nodes 23 and the current flows out from the node 2 and can be considered to flow into the node 3, 1 is arranged to the row of the node 2, and −1 is arranged to the row of the node 3.

For the current vector vtI₀ ^(m+1), the current I_(ij0) ^(m+1) flowing between the respective nodes (in this case, between the nodes 12) to which the current source is not connected and the current I_(i0) ^(m+1) flowing in the respective transmission lines (1 to 3 in this case) can be divided into a vector v_(I0) ^(m+1) which is an element and a vector vI_(J0) ^(m+1) which is a current I_(Jij0) ^(m+1) flowing between nodes (in this case, between nodes 23) to which the current source is connected as an element. For example, when the current source flowing from the node 2 to the node 3 is inserted instead of the resistor r₂₃ between the nodes 2 and 3 on the power supply side in the configuration of FIG. 1, the vector vI_(J0) ^(m+1) is expressed as follows.

$\begin{matrix} \left\lbrack {{Math}.\mspace{14mu} 71} \right\rbrack & \; \\ {{vI}_{0}^{m + 1} = \begin{pmatrix} I_{12_{0}^{m + 1}} & I_{1_{0}^{m + 1}} & I_{2_{0}^{m + 1}} & I_{3_{0}^{m + 1}} \end{pmatrix}^{T}} & (77) \\ \left\lbrack {{Math}.\mspace{14mu} 2} \right\rbrack & \; \\ {{vI}_{J_{0}}^{m + 1} = \left( I_{J_{23}^{m + 1}} \right)^{T}} & (78) \end{matrix}$

Based on the above, Equation (74) can be rewritten as follows.

$\begin{matrix} \left\lbrack {{Math}.\mspace{14mu} 73} \right\rbrack & \; \\ {{\left( {A_{d}\mspace{14mu} A_{dJ}} \right)\begin{pmatrix} {vI}_{0}^{m + 1} \\ {vI}_{J_{0}}^{m + 1} \end{pmatrix}} = 0} & (79) \end{matrix}$

This equation corresponds to Equation (63) and is a conditional expression when the current source is included in the circuit. Therefore, in this case, the value of the scalar potential U and the current I at the boundary condition of k =0 can be obtained by solving the simultaneous equations of Equations (51), (62), and (79). Equations (51), (62), and (79) can be collectively represented in the form of a matrix as follows, and this equation corresponds to Equation (64) in a case where the current source is not included in the circuit and is an expression in a case where the current source is included in the circuit.

$\begin{matrix} {\mspace{79mu} \left\lbrack {{Math}.\mspace{14mu} 74} \right\rbrack} & \; \\ {{\begin{pmatrix} A_{d}^{T} & {- Z_{d}} \\ 0 & A_{d} \end{pmatrix}\begin{pmatrix} {Uv}_{0}^{m + 1} \\ {vI}_{0}^{m + 1} \end{pmatrix}} = {{{- \begin{pmatrix} {\gamma_{d} \cdot A_{d}^{T}} & {{- \delta_{d}} \cdot Z_{d}} \\ 0 & 0 \end{pmatrix}}\begin{pmatrix} {Uv}_{0}^{m} \\ {{vI}_{0}^{m} - {2\; {vI}_{1/2}^{m + {1/2}}}} \end{pmatrix}} + \begin{pmatrix} {{Vv}^{m + 1} + {Vv}^{m}} \\ {{- A_{dJ}} \cdot {vI}_{J_{0}}^{m + 1}} \end{pmatrix}}} & (80) \end{matrix}$

As can be sees from the comparison with Equation (64), the part related to the current source in Equation (80) is only the second row of the second term on the right side. Then, if the current source is not inserted, when the matrix of all 0 is assigned as A_(dJ) and the vector of all 0 is substituted as VI_(J0) ^(m+1), it is exactly the same as Equation (64). That is, Equation (80) can be applied regardless of whether the current source is inserted.

In calculating the values of U and I, Equation (80) is transformed as follows, so that the values of U and I at time (m+1)Δt can be obtained from the values of U and I at the preceding time mΔt or (m+1/2)Δt.

$\begin{matrix} {\mspace{79mu} \left\lbrack {{Math}.\mspace{14mu} 75} \right\rbrack} & \; \\ {\begin{pmatrix} {Uv}_{0}^{m + 1} \\ {vI}_{0}^{m + 1} \end{pmatrix} = {{{- \begin{pmatrix} A_{d}^{T} & {- Z_{d}} \\ 0 & A_{d} \end{pmatrix}^{- 1}}\begin{pmatrix} {\gamma_{d} \cdot A_{d}^{T}} & {{- \delta_{d}} \cdot Z_{d}} \\ 0 & 0 \end{pmatrix}\begin{pmatrix} {Uv}_{0}^{m} \\ {{vI}_{0}^{m} - {2\; {vI}_{1/2}^{m + {1/2}}}} \end{pmatrix}} + {\begin{pmatrix} A_{d}^{T} & {- Z_{d}} \\ 0 & A_{d} \end{pmatrix}^{- 1}\begin{pmatrix} {{Vv}^{m + 1} + {Vv}^{m}} \\ {{- A_{dJ}} \cdot {vI}_{J_{0}}^{m + 1}} \end{pmatrix}}}} & (81) \end{matrix}$

Equations (64) and (80) can also be used in so-called lumped constant circuits in which transmission lines are not included. In that case, an equation may be created by using irreducible representation of the connection matrix. In addition, since Equations (64) and (80) are equations consisting of a matrix including partial matrices, the positions of the partial matrices and partial vectors may be substituted as necessary. Even when there is a subordinate power supply that is a model of a transistor or an operational amplifier, it is possible to deal with it by rewriting Equations (64) and (80) as necessary.

<Calculation at Boundary Condition (k=N)>

The value of the scalar potential U and the current I at the boundary condition of k=N can be obtained by solving the simultaneous equations of Equations (54), (62), and (63). The same method can also be applied to a case where the elements are mutual inductors or cascaded power supplies. For example, Equations (54), (62), and (63) can be collectively represented in the form of the following matrix.

$\begin{matrix} {\mspace{79mu} \left\lbrack {{Math}.\mspace{14mu} 76} \right\rbrack} & \; \\ {{\begin{pmatrix} A_{d}^{T} & {- Z_{d}} \\ 0 & A_{d} \end{pmatrix}\begin{pmatrix} {Uv}_{N}^{m + 1} \\ {vI}_{N}^{m + 1} \end{pmatrix}} = {{{- \begin{pmatrix} {\gamma_{d} \cdot A_{d}^{T}} & {{- \delta_{d}} \cdot Z_{d}} \\ 0 & 0 \end{pmatrix}}\begin{pmatrix} {Uv}_{N}^{m} \\ {{vI}_{N}^{m} - {2\; {vI}_{N - {1/2}}^{m + {1/2}}}} \end{pmatrix}} + \begin{pmatrix} {{Vv}^{m + 1} + {Vv}^{m}} \\ 0 \end{pmatrix}}} & (82) \end{matrix}$

Similarly to A_(d) of Equation (64), A_(d) in Equation (82) is a connection matrix indicating the presence or absence of involvement in each node connection at each node and the presence or absence of connection with each transmission line. For example, in the configuration of FIG. 1, five nodes (1 to 5) indicated by solid circles can be conceived on the load side where k=N (x=w). These are regarded as the row direction, and the presence or absence of involvement with the inter-node connection (in this case, between the nodes 14, 42, 23, 45, and 53) and the presence or absence of connection with the three transmission lines (1 to 3) are expressed in the column direction as follows.

$\begin{matrix} \left\lbrack {{Math}.\mspace{14mu} 77} \right\rbrack & \; \\ {A_{d} = \begin{pmatrix} 1 & 0 & 0 & 0 & 0 & {- 1} & 0 & 0 \\ 0 & {- 1} & 1 & 0 & 0 & 0 & {- 1} & 0 \\ 0 & 0 & {- 1} & 0 & {- 1} & 0 & 0 & {- 1} \\ {- 1} & 1 & 0 & 1 & 0 & 0 & 0 & 0 \\ 0 & 0 & 0 & {- 1} & 1 & 0 & 0 & 0 \end{pmatrix}} & (83) \end{matrix}$

Z_(d) in Equation (82) is a matrix with the impedance Z_(ij) between the nodes and the characteristic impedance Zc_(ij) between the transmission lines as elements. For example, in the configuration of FIG. 1, on the load side where k=N (x=w), Z_(d) is expressed as follows.

$\begin{matrix} \left\lbrack {{Math}.\mspace{14mu} 78} \right\rbrack & \; \\ {A_{d} = \begin{pmatrix} R_{14} & 0 & 0 & 0 & 0 & 0 & 0 & 0 \\ 0 & R_{42} & 0 & 0 & 0 & 0 & 0 & 0 \\ 0 & 0 & R_{23} & 0 & 0 & 0 & 0 & 0 \\ 0 & 0 & 0 & R_{45} & 0 & 0 & 0 & 0 \\ 0 & 0 & 0 & 0 & R_{53} & 0 & 0 & 0 \\ 0 & 0 & 0 & 0 & 0 & {Zc}_{11} & {Zc}_{12} & {Zc}_{13} \\ 0 & 0 & 0 & 0 & 0 & {Zc}_{21} & {Zc}_{22} & {Zc}_{23} \\ 0 & 0 & 0 & 0 & 0 & {Zc}_{31} & {Zc}_{32} & {Zc}_{33} \end{pmatrix}} & (84) \end{matrix}$

For example, in the configuration of FIG. 1, on the load side where k=N (x=w), vI₀ ^(m+1) in Equation (82) is expressed as follows.

[Math. 79]

vI _(N) ^(m+1)=(I ₁₄ _(N) ^(m+1) I ₄₂ _(N) ^(m+1) I ₂₃ _(N) ^(m+1) I ₄₅ _(N) ^(m+1) I ₅₃ _(N) ^(m+1) I ₁ _(N) ^(m+1) I ₂ _(N) ^(m+1) I ₃ _(N) ^(m+1)) ^(T)   (85)

γ_(d) and δ_(d) in Equation (82) are diagonal matrices with γ and δ corresponding to the type of elements connected between nodes as elements. For example, in the configuration of FIG. 1, since all resistors R are connected, γ_(d) and δ_(d) are expressed on the load side where k=N (x=w) as follows.

$\begin{matrix} \left\lbrack {{Math}.\mspace{14mu} 80} \right\rbrack & \; \\ {\gamma_{d} = \begin{pmatrix} 1 & 0 & 0 & 0 & 0 & 0 & 0 & 0 \\ 0 & 1 & 0 & 0 & 0 & 0 & 0 & 0 \\ 0 & 0 & 1 & 0 & 0 & 0 & 0 & 0 \\ 0 & 0 & 0 & 1 & 0 & 0 & 0 & 0 \\ 0 & 0 & 0 & 0 & 1 & 0 & 0 & 0 \\ 0 & 0 & 0 & 0 & 0 & {- 1} & 0 & 0 \\ 0 & 0 & 0 & 0 & 0 & 0 & {- 1} & 0 \\ 0 & 0 & 0 & 0 & 0 & 0 & 0 & {- 1} \end{pmatrix}} & (86) \\ \left\lbrack {{Math}.\mspace{14mu} 81} \right\rbrack & \; \\ {\delta_{d} = \begin{pmatrix} 1 & 0 & 0 & 0 & 0 & 0 & 0 & 0 \\ 0 & 1 & 0 & 0 & 0 & 0 & 0 & 0 \\ 0 & 0 & 1 & 0 & 0 & 0 & 0 & 0 \\ 0 & 0 & 0 & 1 & 0 & 0 & 0 & 0 \\ 0 & 0 & 0 & 0 & 1 & 0 & 0 & 0 \\ 0 & 0 & 0 & 0 & 0 & 1 & 0 & 0 \\ 0 & 0 & 0 & 0 & 0 & 0 & 1 & 0 \\ 0 & 0 & 0 & 0 & 0 & 0 & 0 & 1 \end{pmatrix}} & (87) \end{matrix}$

vI_(N−1/2) ^(m+1/2) in Equation (82) is expressed as follows.

[Math. 82]

vI _(N−1/2) ^(m+1/2)=(0 0 0 0 0 I ₁ _(N−1/2) ^(m+1/2) I ₂ _(N−1/2) ^(m+1/2) I ₃ _(N−1/2) ^(m+1/2))^(T)   (88)

On the other hand, Vv^(m) in Equation (82) is expressed as follows.

[Math. 83]

Vv ^(m)=(V ₁₄ ^(m) V ₄₂ ^(m) V ₂₃ ^(m) V ₄₅ ^(m) V ₅₃ ^(m) 0 0 0)^(T)   (89)

In calculating the values of U and I, Equation (82) is transformed as follows, so that the values of U and I at time (m+1)Δt can be obtained from the values of U and I at the preceding time mΔt or (m+1/2)Δt.

$\begin{matrix} {\mspace{79mu} \left\lbrack {{Math}.\mspace{14mu} 84} \right\rbrack} & \; \\ {\begin{pmatrix} {Uv}_{N}^{m + 1} \\ {vI}_{N}^{m + 1} \end{pmatrix} = {{{- \begin{pmatrix} A_{d}^{T} & {- Z_{d}} \\ 0 & A_{d} \end{pmatrix}^{- 1}}\begin{pmatrix} {\gamma_{d} \cdot A_{d}^{T}} & {{- \delta_{d}} \cdot Z_{d}} \\ 0 & 0 \end{pmatrix}\begin{pmatrix} {Uv}_{N}^{m} \\ {{vI}_{N}^{m} - {2\; {vI}_{N - {1/2}}^{m + {1/2}}}} \end{pmatrix}} + {\begin{pmatrix} A_{d}^{T} & {- Z_{d}} \\ 0 & A_{d} \end{pmatrix}^{- 1}\begin{pmatrix} {{Vv}^{m + 1} + {Vv}^{m}} \\ 0 \end{pmatrix}}}} & (90) \end{matrix}$

Equation (63) constituting a part of Equation (82) is a conditional expression in a case where the current source is not included in the circuit. Thus, when considering the presence of the current source, Equation (79) may be applied instead of Equation (63), similarly to the calculation at the boundary condition (k=0). Therefore, in this case, the value of the scalar potential U and the current I at the boundary condition of k=N can be obtained by solving the simultaneous equations of Equations (54), (62), and (79). Equations (54), (62), and (79) can be collectively represented in the form of a matrix as follows, and this equation corresponds to Equation (82) in a case where the current source is not included in the circuit and s an expression in a case where the current source is included in the circuit.

$\begin{matrix} {\mspace{79mu} \left\lbrack {{Math}.\mspace{14mu} 85} \right\rbrack} & \; \\ {{\begin{pmatrix} A_{d}^{T} & {- Z_{d}} \\ 0 & A_{d} \end{pmatrix}\begin{pmatrix} {Uv}_{N}^{m + 1} \\ {vI}_{N}^{m + 1} \end{pmatrix}} = {{{- \begin{pmatrix} {\gamma_{d} \cdot A_{d}^{T}} & {{- \delta_{d}} \cdot Z_{d}} \\ 0 & 0 \end{pmatrix}}\begin{pmatrix} {Uv}_{N}^{m} \\ {{vI}_{N}^{m} - {2\; {vI}_{N - {1/2}}^{m + {1/2}}}} \end{pmatrix}} + \begin{pmatrix} {{Vv}^{m + 1} + {Vv}^{m}} \\ {{- A_{dJ}} \cdot {vI}_{J_{N}}^{m + 1}} \end{pmatrix}}} & (91) \end{matrix}$

As can be seen from the comparison with Equation (82), the part related to the current source in Equation (89) is only the second row of the second term on the right side. Then, if the current source is not inserted, when the matrix of all 0 is assigned as A_(dJ) and the vector of all 0 is substituted as vI_(JN) ^(m+1), it is exactly the same as Equation (82). That is, Equation (91) can be applied regardless of whether the current source is inserted.

In calculating the values of U and I, Equation (91) is transformed as follows, so that the values of U and I at time (m+1)Δt can be obtained from the values of U and I at the preceding time mΔt or (m+1/2)Δt.

     [Math.  86] $\begin{matrix} {\begin{pmatrix} {Uv}_{N}^{m + 1} \\ {vI}_{N}^{m + 1} \end{pmatrix} = {{{- \begin{pmatrix} A_{d}^{T} & {- Z_{d}} \\ 0 & A_{d} \end{pmatrix}^{- 1}}\begin{pmatrix} {\gamma_{d} \cdot A_{d}^{T}} & {{- \delta_{d}} \cdot Z_{d}} \\ 0 & 0 \end{pmatrix}\begin{pmatrix} {Uv}_{N}^{m} \\ {{vI}_{N}^{m} - {2{vI}_{N - {1\text{/}2}}^{m + {1\text{/}2}}}} \end{pmatrix}} + {\begin{pmatrix} A_{d}^{T} & {- Z_{d}} \\ 0 & A_{d} \end{pmatrix}^{- 1}\begin{pmatrix} {{Vv}^{m + 1} + {Vv}^{m}} \\ {{- A_{dJ}} \cdot {vI}_{J_{N}}^{m + 1}} \end{pmatrix}}}} & (92) \end{matrix}$

Equations (82) and (91) can also be used in so-called lumped constant circuits in which transmission lines are not included. In that case, an equation may be created by using irreducible representation of the connection matrix. In addition, since Equations (82) and (91) are equations consisting of a matrix including partial matrices, the positions of the partial matrices and partial vectors may be substituted as necessary. Even when there is a subordinate power supply that is a model of a transistor or an operational amplifier, it is possible to deal with it by rewriting Equations (82) and (91) as necessary.

<Calculation of Antenna Term>

In calculating the values of the antenna terms ˜U and ˜A by the FDTD method,

[Math.  87] $\begin{matrix} {{{\,^{\sim}U}\left( {t,x} \right)} = {\frac{1}{4{\pi ɛ}}{\int_{0}^{w}{{dx}^{\prime}{\frac{{Q_{t}\left( {{t - {\sqrt{\left| {x - x^{\prime}} \right|}\text{/}c}},x^{\prime}} \right)} - {Q_{t}\left( {t,x} \right)}}{\left| {x - x^{\prime}} \right|}\left\lbrack {{Math}.\mspace{14mu} 88} \right\rbrack}}}}} & (11) \\ {{{\,^{\sim}A}\left( {t,x} \right)} = {\frac{\mu}{4\pi}{\int_{0}^{w}{{dx}^{\prime}\frac{{I_{t}\left( {{t - {\sqrt{\left| {x - x^{\prime}} \right|}\text{/}c}},x^{\prime}} \right)} - {I_{t}\left( {t,x} \right)}}{\left| {x - x^{\prime}} \right|}}}}} & (12) \end{matrix}$

are discretized.

For example, at the position x=k·Δx on each transmission line and time t=m·Δt, Equation (11) can be discretized as follows.

     [Math.  89] $\begin{matrix} {{{}_{}^{}{}_{}^{m + 1}} = {\frac{1}{4{\pi ɛ}}\left\lbrack {{\Sigma_{k^{\prime} = 0}^{k}\frac{{Qt}_{k\; \prime}^{m + 1 - {({k - k^{\prime}})}} - {Qt}_{k}^{m + 1}}{k - {k\; \prime}}} + {\Sigma_{k^{\prime} = k}^{N}\frac{{Qt}_{k\; \prime}^{m + 1 + {({k - k^{\prime}})}} - {Qt}_{k}^{m + 1}}{- \left( {k - k^{\prime}} \right)}}} \right\rbrack}} & (93) \end{matrix}$

Here, when Qt_(k) ^(m) is the total charge of all the transmission lines at the position x=·Δx and the time t=m·Δt on the transmission line, and It_(k) ^(m) is the total current on all the transmission lines at the position x=k·Δx on the transmission line and the time t=m·Δt, Qt_(k) ^(m+1) can be calculated by, for example,

[Math.  90] $\begin{matrix} {{\frac{{Qt}_{k}^{m + 1} - {Qt}_{k}^{m}}{\Delta \; t} + \frac{{It}_{k + {1\text{/}2}}^{m + {1\text{/}2}} - {It}_{k - {1\text{/}2}}^{m + {1\text{/}2}}}{\Delta \; x}} = 0} & (94) \end{matrix}$

In addition, at a position x=(k+1/2)·Δx on the transmission line and time t=(m+1/2)·Δt, Equation (12) can be discretized as follows.

     [Math.  91] $\begin{matrix} {{{}_{}^{}{}_{k + {1\text{/}2}}^{m + {1\text{/}2}}} = {\frac{\mu}{4\pi}\left\lbrack {{\Sigma_{k^{\prime} = 0}^{k}\frac{{It}_{k^{\prime} + {1\text{/}2}}^{m + {1\text{/}2} - {({k - k^{\prime}})}} - {It}_{k + {1\text{/}2}}^{m + {1\text{/}2}}}{k - {k\; \prime}}} + {\Sigma_{k^{\prime} = k}^{N}\frac{{It}_{k^{\prime} + {1\text{/}2}}^{m + {1\text{/}2} + {({k - k^{\prime}})}} - {It}_{k + {1\text{/}2}}^{m + {1\text{/}2}}}{- \left( {k - k^{\prime}} \right)}}} \right\rbrack}} & (95) \end{matrix}$

Therefore, values of ˜U and ˜A can be calculated from previously given or previously calculated charge and current values.

<Overall Calculation Procedure>

The overall procedure of calculating the potential and current in the multi-conductor transmission line constituting the distributed constant circuit, the potential and current in the element constituting the lumped constant circuit connected to the multi-conductor transmission line, and the electromagnetic field including noise generated from each circuit will be described with reference to FIG. 2.

Prior to the calculation, the circuit configuration such as arrangement of elements and nodes is specified, and initial values of potential, current, charge, and antenna term are set for each transmission line and each element (S1). The initial value is set for a parameter value which is not obtained prior to calculation by each of the following calculation expressions at m=0. In addition, if there is a power supply between the nodes, the value is preset.

Subsequently, the potential, the current, the charge, and the antenna term are calculated (S2).

First, the calculation is performed at m=0. Note that the order of calculation may be appropriately changed according to how to set the initial value or the like.

First, Uv₀ ¹ and vI₀ ¹ are calculated by Equation (81) (S2-1). Next, in the case of k=0 in Equation (94), an initial value is substituted into each parameter to calculate Qt₀ ¹ (S2-2). In this case, It_(k−1/2) ^(1/2) becomes It_(−1/2) ^(1/2) when k=0 and it is out of the definition range of the grid (x<0). In this case, an initial value may be given, but (I₀ ¹+I₀ ⁰)/2 may be obtained from I₀ ¹ calculated in S2-1 and I₀ ⁰ given as the initial value so that it falls within the definition range and the error is small.

Next, in the case of k=0 in Equation (93), the initial value and the calculation result of Qt₀ ¹ obtained in S2-2 are substituted into each parameter to calculate ˜U₀ ¹ (S2-3). Then, for each case of k=1, 2, . . . , N−1 in Equation (94), the initial values are substituted into the respective parameters to calculate Qt₁ ¹, Qt₂ ¹, . . . Qt_(N−1) ¹ (S2-4).

Next, for each case of k=1, 2, . . . , N−1 in Equation (93), the initial value and the calculation result of Qt_(k) ¹ obtained in S2-4 are substituted into each parameter to calculate ˜U₁ ¹, ˜U₂ ¹, . . . ˜U_(N−1) ¹ respectively (S2-5).

Next, for each case of k=1, 2, . . . , N−1 in Equation (47), the initial values are substituted into each parameter and calculation results of ˜U_(k)1 obtained in S2-5 to calculate Uv₁ ¹, Uv₂ ¹, . . . Uv_(N−1) ¹ (S2-6).

Next, Uv_(N) ¹ and vI_(N) ¹ are calculated by substituting the initial value into each parameter by Equation (92) (S2-7).

Next, in the case of k=N in Equation (94), an initial value is substituted into each parameter to calculate Qt_(N) ¹ (S2-8). In this case, It_(k+1/2) ^(1/2) becomes It_(N+1/2) ^(1/2) when k=N and it is out of the definition range of the grid (x>w) In this case, an initial value may be given, but (I_(N) ¹+I_(N) ⁰) may be obtained from I_(N) ¹ calculated in S2-7 and I_(N) ⁰ given as the initial value so that it falls within the definition range and the error is small.

Next, with respect to the case of k=N in Equation (93), the initial value, the calculation result of Qt₀ ¹ obtained in S2-2, the calculation result of Qt_(k) ¹ obtained in S2-4, and the calculation result of Qt_(N) ¹ obtained in S2-8 are substituted into each parameter to calculate ˜U_(N) ¹ (S2-9).

Next, for each case of k=0, 1, . . . , N−1 in Equation (95), the initial value is substituted into each parameter to calculate ˜A_(1/2) ^(1/2), ˜A_(3/2) ^(1/2), . . . ˜A_(N−1/2) ^(1/2) respectively (S2-10).

Next, for each case of k=0, 1, . . . , N−1 in Equation (48), the initial value, the calculation result of Uv_(k) ¹ obtained in S2-6, and the calculation result of ˜A_(k+1/2) ^(1/2) obtained in S2-10 are substituted into each parameter to calculate I_(v1/2) ^(3/2), I_(v3/2) ^(3/2), . . . , I_(vN−1/2) ^(3/2) (S2-11).

Subsequently, the calculation is performed at m=1. As long as the parameter values necessary for calculation are already calculated, the order of calculation may be changed as appropriate.

First, the calculation results of Uv₀ ¹ and vI₀ ¹ obtained in S2-1 and the calculation result of I_(1/2) ^(3/2) obtained in S2-11 are substituted into each parameter of Equation (81) to calculate Uv₀ ² and vI₀ ² (S2-12).

Next, in the case of k=0 in Equation (94), the calculation result of Qt₀ ¹ obtained in S2-2 and the calculation result of I_(1/2) ^(3/2) obtained in S2-11 are substituted into each parameter to calculate Qt₀ ² (S2-13). In this case, It_(k−1/2) ^(3/2) becomes It_(−1/2) ^(3/2) when k=0 and it is out of the definition range of the grid (x<0). Therefore, the initial value maybe given, but (I₀ ²+I₀ ¹)/2 may be obtained from I₀ ² calculated in S2-12 and I₀ ¹ calculated in S2-1 so that it falls within the definition range and the error is small.

Next, with respect to the case of k=0 in Equation (93), the initial value, the calculation result of Qt₀ ¹ obtained in S2-2, the calculation result of Qt_(k) ¹ obtained in S2-4, and the calculation result of Qt_(N) ¹ obtained in S2-8 are substituted into each parameter to calculate ˜U₀ ² (S2-14).

Next, for each case of k=1, 2, . . . , N−1 in Equation (94), the calculation result of Qt_(k) ¹ obtained in S2-4 and the calculation result of I_(k−1/2) ^(3/2) obtained in S2-11 are substituted into each parameter to calculate Qt₁ ², Qt₂ ², . . . Qt_(N−1) ² respectively (S2-15).

Next, for each case of k=1, 2, . . . , N−1 in Equation (93), the initial value, the calculation result of Qt_(k) ¹ obtained in S2-4, and the calculation result of Qt_(k) ² obtained in S2-15 are substituted into each parameter to calculate ˜U₁ ², ˜U₂ ², . . . ˜U_(N−1) ² (S2-16).

Next, for each case of k=1, 2, . . . , N−1 in Equation (47), the calculation result of ˜U_(k) ¹ obtained in S2-5, the calculation result of Uv_(k) ¹ obtained in S2-6, the calculation result of I_(k−1/2) ^(3/2) obtained in S2-11, and the calculation result of ˜U_(k) ² obtained in S2-16 are substituted into each parameter to calculate Uv₁ ², Uv₂ ², . . . Uv_(N−1) ² respectively (S2-17).

Next, the calculation results of Uv_(N) ¹ and vI_(N) ¹ obtained in S2-7 and the calculation result of I_(N−1/2)3/2 obtained in S2-11 are substituted into each parameter of Equation (92) to calculate Uv_(N) ² and vI_(N) ² (S2-18).

Next, in the case of k=N in Equation (94), the calculation result of Qt_(N) ¹ obtained in S2-8 and the calculation result of I_(N−1/2) ^(3/2) obtained in S2-11 are substituted into each parameter to calculate Qt_(N) ² (S2-19). In this case, It_(k+1/2) ^(3/2) becomes It_(N+1/2) ^(3/2) when k=N and it is out of the definition range of the grid (x>w). Therefore, the initial value maybe given, but (I_(N) ²+I_(N) ¹)/2 may be obtained from I_(N) ² calculated in S2-18 and I_(N) ¹ calculated in S2-7 so that it falls within the definition range and the error is small.

Next, for the case of k=N in Equation (93), the initial value, the calculation result of Qt₀ ¹ obtained in S2-2, the calculation result of Qt_(k) ¹ obtained in S2-4, the calculation result of Qt_(N) ¹ obtained in S2-9, the calculation result of Qt₀ ² obtained in S2-13, the calculation result of Qt_(k) ² obtained in S2-15, and the calculation result of Qt_(N) ² obtained in S2-19 are substituted into each parameter to calculate ˜U_(N) ² (S2-20). Next, in each case of k=0, 1, . . . , N−1 in Equation (95), the calculation result of I_(k+1/2) ^(3/2) obtained in S11 is substituted into each parameter to calculate ˜A_(1/2) ^(3/2), ˜A_(3/2) ^(3/2), . . . ˜A_(N−1/2) ^(3/2) (S2-21).

Next, for each case of k=0, 1, . . . , N−1 in Equation (48), the calculation result of ˜A_(k+1/2) ^(1/2) obtained in S2-10, the calculation result of I_(k+1/2) ^(3/2) obtained in S2-11, the calculation result of Uv₀ ² obtained in S2-12, the calculation result of Uv_(k) ² obtained in S2-17, the calculation result of Uv_(N) ² obtained in S2-18, and the calculation result of ˜A_(k+1/2) ^(3/2) obtained in S2-21 are substituted into each parameter to calculate Iv_(1/2) ^(5/2), Iv_(3/2) ^(5/2), . . . , Iv_(N−1/2) ^(5/2) respectively (S2-22).

Even at m≥2, S2-12 to S2-22 are repeatedly executed up to a predetermined value m while increasing m by 1, and Uv₀ ^(m+1), vI₀ ^(m+1), Qt₀ ^(m+1), ˜U₀ ^(m+1), Qt_(k) ^(m+1), ˜U_(k) ^(m+1), Uv_(k) ^(m+1), Uv_(N) ^(m+1), vI_(N) ^(m+1), Qt_(N) ^(m+1), ˜U_(N) ^(m+1), ˜A_(k+1/2) ^(m+1/2) , and Iv_(k+1/2) ^(m+3/2) are obtained.

As described above, according to the method for calculating the potential, the current, and the peripheral electromagnetic field in the electric circuit according to the present invention, it is possible to comprehensively calculate the potential and the current in the multi-conductor transmission line constituting the distributed constant circuit, the potential and the current in the elements constituting the lumped constant circuit connected to the multi-conductor transmission line, and the electromagnetic field including the noise generated from each circuit, without performing a complicated calculation process.

Each process in the method for calculating the potential, the current, and the peripheral electromagnetic field in the electric circuit according to the present invention maybe merged, divided, or changed in order as necessary. In addition, appropriately changes can be made thereto within the scope of the technical idea expressed in the present invention, and such modifications or improvements also fall within the technical scope of the present invention.

When causing a computer to execute the method for calculating the potential, the current, and the peripheral electromagnetic field in the electric circuit according to the present invention, the processing contents in each processing step are described by a program. The program is stored in, for example, a hard disk device, and at the time of execution, necessary programs and data are read into a random access memory (RAM), and the program is executed by a CPU, whereby each processing contents are realized on the computer. 

1. A method for calculating a potential, a current, and a peripheral electromagnetic field in an electric circuit, which causes a computer to calculate a potential and a current in a multi-conductor transmission line constituting a distributed constant circuit, a potential and a current in an element constituting a lumped constant circuit connected to the multi-conductor transmission line, and an electromagnetic radiation amount from each circuit, the method comprising: inputting a circuit configuration of the distributed constant circuit and the lumped constant circuit and an initial value of each variable; and obtaining the potential and the current in the multi-conductor transmission line, the potential and the current in the element, and the electromagnetic radiation amount by solving: under the circuit configuration and the initial value, the following basic equations of new transmission theory: [Math.  1] $\begin{matrix} {\frac{\partial{U_{i}\left( {t,x} \right)}}{\partial t} = {{{- \Sigma_{j = 1}^{n}}{P_{ij} \cdot \frac{\partial{{Ij}\left( {t,x} \right)}}{\partial x}}} + {\frac{\partial{{\,^{\sim}U}\left( {t,x} \right)}}{\partial t}\left\lbrack {{Math}.\mspace{14mu} 2} \right\rbrack}}} & (1) \\ {\frac{\partial{U_{i}\left( {t,x} \right)}}{\partial x} = {{{- \Sigma_{j = 1}^{n}}{L_{ij} \cdot \frac{\partial{I_{j}\left( {t,x} \right)}}{\partial t}}} - \frac{\partial{{\,^{\sim}A}\left( {t,x} \right)}}{\partial t} - {R_{i} \cdot {{I_{i}\left( {t,x} \right)}\left\lbrack {{Math}.\mspace{14mu} 3} \right\rbrack}}}} & (2) \\ {{{\,^{\sim}U}\left( {t,x} \right)} = {\frac{1}{4{\pi ɛ}}{\int_{0}^{w}{{dx}^{\prime}{\frac{{Q_{t}\left( {{t - {\sqrt{\left| {x - x^{\prime}} \right|}\text{/}c}},x^{\prime}} \right)} - {Q_{t}\left( {t,x} \right)}}{\left| {x - x^{\prime}} \right|}\left\lbrack {{Math}.\mspace{14mu} 4} \right\rbrack}}}}} & (3) \\ {{{\,^{\sim}A}\left( {t,x} \right)} = {\frac{\mu}{4\pi}{\int_{0}^{w}{{dx}^{\prime}\frac{{I_{t}\left( {{t - {\sqrt{\left| {x - x^{\prime}} \right|}\text{/}c}},x^{\prime}} \right)} - {I_{t}\left( {t,x} \right)}}{\left| {x - x^{\prime}} \right|}}}}} & (4) \end{matrix}$ (t is a time, x and x′ are positions on each transmission line (x>x′), i, j (=1, 2, . . . , n) is the number of each transmission line, U_(i)(t, x) and A_(i)(t, x) are scalar potential (potential) and vector potential of a transmission line i at time t and a position x, respectively, I_(j)(t, x) is a current flowing in a transmission line j at the time t and the position x, P_(ij) and L_(ij) are a potential coefficient and an induction coefficient between the transmission lines i and j respectively, R_(i) is a resistance per unit length of the transmission line i, ˜U(t, x) and ˜A(t, x) are antenna terms indicating the electromagnetic radiation amount at the time t and the position x, ε is a permittivity, μ is a permeability, and Q_(t)(t, x) and I_(t)(t, x) are a charge and a current of all transmission lines at the time t and the position x) using a boundary condition formula at x=0 and w which are boundaries between the distributed constant circuit and the lumped constant circuit: U _(i)(t,x)−U _(j)(t,x)=V _(ij)(t)+Z _(ij) ·Δ·I _(ij)(t)   (5), and Kirchhoff s current law, that is, a summation formula in which an algebraic sum of branch currents of all the branches flowing into one node is zero, that is, a current flowing out from the node is positive and a current entering the node is negative: α·I _(i)(t,x)+Σ_(j(≠i)) I _(ij)(t)=0   (6) (V_(ij)(t) is a power supply voltage connected between the transmission line or the nodes i, j (≠i) at the time t on the lumped constant circuit side, I_(ij)(t) is a current flowing between the transmission lines or from the node i to the node (≠i) at the time t on the lumped constant circuit side, Z_(ij) is a load connected between the transmission lines or the nodes i, j (≠i), Δ is 1 when Z_(ij)=d/dt when Z_(ij)=L_(ij), and (d/dt)⁻¹ when Z_(ij)=1/C_(ij), and α is 1 when x=0 and −1 when x=w).
 2. The method for calculating the potential, the current, and the peripheral electromagnetic field in the electric circuit according to claim 1, wherein in the obtaining of the potential and the current in the multi-conductor transmission line, the basic equation is solved by using an FDTD method.
 3. The method for calculating the potential, the current, and the peripheral electromagnetic field in the electric circuit according to claim 2, wherein when a scalar potential at a position x=k·Δx (k=0, 1, . . . , N, w=N·Δx) and time t=m·Δt (m=0, 1, . . . , arbitrary) on the transmission line i is U_(k) ^(m), a current is denoted as I_(k) ^(m), Uv_(k) ^(m) is a vector with U_(k) ^(m) as an element for each transmission line i, Iv_(k) ^(m) is a vector whose elements are I_(k) ^(m) for each transmission line i, P_(d) is a matrix whose elements are P_(ij), L_(d) is a matrix whose elements are L_(ij), and R_(d) is a matrix whose diagonal element is R_(i), in Equation (1), [Math.  5] $\begin{matrix} {\frac{{Uv}_{k}^{m + 1} - {Uv}_{k}^{m}}{\Delta \; t} = {{{- P_{d}}\frac{{Iv}_{k + {1\text{/}2}}^{m + {1\text{/}2}} - {Iv}_{k - {1\text{/}2}}^{m + {1\text{/}2}}}{\Delta \; x}} + \frac{{{}_{}^{}{}_{}^{m + 1}} - {{}_{}^{}{}_{}^{}}}{\Delta \; t}}} & (7) \end{matrix}$ a discretized equation is used, and in Equation (2)      [Math.  6] $\begin{matrix} {\frac{{Uv}_{k + 1}^{m + 1} - {Uv}_{k}^{m + 1}}{\Delta \; x} = {{{- L_{d}}\frac{{Iv}_{k + {1\text{/}2}}^{m + {3\text{/}2}} - {Iv}_{k + {1\text{/}2}}^{m + {1\text{/}2}}}{\Delta \; t}} - \frac{{{}_{}^{}{}_{k + {1\text{/}2}}^{m + {1\text{/}2}}} - {{}_{}^{}{}_{k + {1\text{/}2}}^{m - {1\text{/}2}}}}{\Delta \; t} - {R_{d}\frac{{Iv}_{k + {1\text{/}2}}^{m + {3\text{/}2}} - {Iv}_{k + {1\text{/}2}}^{m + {1\text{/}2}}}{2}}}} & (8) \end{matrix}$ a discretized equation is used.
 4. The method for calculating the potential, the current, and the peripheral electromagnetic field in the electric circuit according to claim 3, wherein when Zc_(d) is a matrix having a characteristic impedance Zc_(ij) between the transmission lines i and j as an element, Equation (7) is used when k=0 which is a boundary of one of the distributed constant circuit and the lumped constant circuit, [Math. 7] Uv ₀ ^(m+1) −Zc _(d) ·Iv ₀ ^(m+1) =Uv ₀ ^(m) +Zc _(d)·(Iv ₀ ^(m)−2Iv _(1/2) ^(m+1/2))   (9) and, at k=N which is the other boundary, [Math. 8] Uv_(N) ^(m+1) −Zc _(d) ·Iv _(N) ^(m+1) =Uv _(N) ^(m) +Zc _(d)·(Iv _(N) ^(m)−2Iv _(N−1/2) ^(m+1/2))   (10) Equations (9) and (10) are solved using the following discretized boundary condition formulas for k=0 and N corresponding to Equations (5) and (6), [Math. 9] (U _(i) ^(m+1) −U _(j) ^(m+1))−Z _(ij) ·I _(ij) ^(m+1)=−γ_(ij)(U _(i) ^(m) −U _(j) ^(m))+δ_(ij) ·Z _(ij) ·I _(ij) ^(m) +V _(ij) ^(m+1) +V _(ij) ^(m)    (11) (when Z_(ij)=R_(ij), γ=1 and δ=1, when Z_(ij)=2L_(ij)/Δt, γ=1 and δ=−1, and when Z_(ij)=Δt/2C_(ij), γ=−1 and δ=1) [Math. 10] β·I _(j) ^(m+1)+Σ_(j(≠i)) I _(ij) ^(m+1)=0   (12) (β is 1 when k=0 and −1 when k=N).
 5. The method for calculating the potential, the current, and the peripheral electromagnetic field in the electric circuit according to claim 4, wherein when a connection matrix indicating the presence or absence of involvement in each node connection and the presence or absence of connection with each transmission line in each node is A_(d), a vector having the current flowing between the respective nodes and the current I_(i) flowing through each transmission line as an element is vI_(k) ^(m), a matrix having elements of the impedance Z_(ij) between the respective nodes and the characteristic impedance Zc_(ij) between the transmission lines is Z_(d), diagonal matrices with 65 and 67 as elements corresponding to a type of elements connected between the nodes are γ_(d) and δ_(d), and a vector having the voltage V_(ij) applied between the nodes as an element is Vv, Equations (9), (11), and (12) are expressed in a form of a matrix:      [Math.  11] $\begin{matrix} {{\begin{pmatrix} A_{d}^{T} & {- Z_{d}} \\ 0 & A_{d} \end{pmatrix}\begin{pmatrix} {Uv}_{0}^{m + 1} \\ {vI}_{0}^{m + 1} \end{pmatrix}} = {{{- \begin{pmatrix} {\gamma_{d} \cdot A_{d}^{T}} & {{- \delta_{d}} \cdot Z_{d}} \\ 0 & 0 \end{pmatrix}}\begin{pmatrix} {Uv}_{0}^{m} \\ {{vI}_{0}^{m} - {2{vI}_{1\text{/}2}^{m + {1\text{/}2}}}} \end{pmatrix}} + \begin{pmatrix} {{Vv}^{m + 1} + {Vv}^{m}} \\ 0 \end{pmatrix}}} & (13) \end{matrix}$ Equations (10), (11), and (12) are expressed in a form of a matrix:      [Math.  12] $\begin{matrix} {{\begin{pmatrix} A_{d}^{T} & {- Z_{d}} \\ 0 & A_{d} \end{pmatrix}\begin{pmatrix} {Uv}_{N}^{m + 1} \\ {vI}_{N}^{m + 1} \end{pmatrix}} = {{{- \begin{pmatrix} {\gamma_{d} \cdot A_{d}^{T}} & {{- \delta_{d}} \cdot Z_{d}} \\ 0 & 0 \end{pmatrix}}\begin{pmatrix} {Uv}_{N}^{m} \\ {{vI}_{N}^{m} - {2{vI}_{N - {1\text{/}2}}^{m + {1\text{/}2}}}} \end{pmatrix}} + \begin{pmatrix} {{Vv}^{m + 1} + {Vv}^{m}} \\ 0 \end{pmatrix}}} & (14) \end{matrix}$ and each equation is solved.
 6. The method for calculating the potential, the current, and the peripheral electromagnetic field in the electric circuit according to claim 5, wherein in Equation (12), [Math.  13] $\begin{matrix} {\left( {A_{d}\mspace{14mu} A_{dJ}} \right) = {\begin{pmatrix} {vI}_{0}^{m + 1} \\ {vI}_{J_{0}}^{m + 1} \end{pmatrix} = 0}} & (15) \end{matrix}$ (A_(d) is a connection matrix indicating the presence or absence of involvement in each node connection not including a current source and the presence or absence of connection with each transmission line in each node, A_(dJ) is a connection matrix indicating the presence or absence of involvement in each node connection including the current source at each node, vI₀ ^(m+1) is a vector whose elements are a current I_(ij0) ^(m+1) flowing between the respective nodes to which no current source is connected and a current I_(i0) ^(m+1) flowing through each transmission line, and vI_(J0) ^(m+1) is a vector whose elements are a current I_(Jij0) ^(m+1) flowing between the nodes to which the current source is connected) is used, and Equations (9), (11), and (15) is expressed in a form of a matrix:      [Math.  14] $\begin{matrix} {{\begin{pmatrix} A_{d}^{T} & {- Z_{d}} \\ 0 & A_{d} \end{pmatrix}\begin{pmatrix} {Uv}_{0}^{m + 1} \\ {vI}_{0}^{m + 1} \end{pmatrix}} = {{{- \begin{pmatrix} {\gamma_{d} \cdot A_{d}^{T}} & {{- \delta_{d}} \cdot Z_{d}} \\ 0 & 0 \end{pmatrix}}\begin{pmatrix} {Uv}_{0}^{m} \\ {{vI}_{0}^{m} - {2{vI}_{1\text{/}2}^{m + {1\text{/}2}}}} \end{pmatrix}} + \begin{pmatrix} {{Vv}^{m + 1} + {Vv}^{m}} \\ {{- A_{dJ}} \cdot {vI}_{J_{0}}^{m + 1}} \end{pmatrix}}} & (16) \end{matrix}$ Equations (10), (11), and (15) are expressed in a form of a matrix:      [Math.  15] $\begin{matrix} {{\begin{pmatrix} A_{d}^{T} & {- Z_{d}} \\ 0 & A_{d} \end{pmatrix}\begin{pmatrix} {Uv}_{N}^{m + 1} \\ {vI}_{N}^{m + 1} \end{pmatrix}} = {{{- \begin{pmatrix} {\gamma_{d} \cdot A_{d}^{T}} & {{- \delta_{d}} \cdot Z_{d}} \\ 0 & 0 \end{pmatrix}}\begin{pmatrix} {Uv}_{N}^{m} \\ {{vI}_{N}^{m} - {2{vI}_{N - {1\text{/}2}}^{m + {1\text{/}2}}}} \end{pmatrix}} + \begin{pmatrix} {{Vv}^{m + 1} + {Vv}^{m}} \\ {{- A_{dJ}} \cdot {vI}_{J_{N}}^{m + 1}} \end{pmatrix}}} & (17) \end{matrix}$ and each equation is solved.
 7. The method for calculating the potential, the current, and the peripheral electromagnetic field in the electric circuit according to claim 6, wherein when a total charge of all the transmission lines at the position x=k·Δx and the time t=m·Δt on the transmission line is Qt_(k) ^(m) and a total current at the position x=k·Δx on the transmission line and the time t=m·Δt is It_(k) ^(m), a value of Qt_(k) ^(m+1) is calculated by [Math.  16] $\begin{matrix} {{\frac{{Qt}_{k}^{m + 1} - {Qt}_{k}^{m}}{\Delta \; t} + \frac{{It}_{k + {1\text{/}2}}^{m + {1\text{/}2}} - {It}_{k - {1\text{/}2}}^{m + {1\text{/}2}}}{\Delta \; x}} = 0} & (18) \end{matrix}$ and a value of an antenna term ˜U at the position x=k·Δx and time t=(m+1)·Δt on each transmission line and a value of an antenna term ˜A at a position x=(k+1/2)·Δx on each transmission line and time t=(m+1/2)·Δt are calculated by the following Equations.      [Math.  17] $\begin{matrix} {{{}_{}^{}{}_{}^{m + 1}} = {{\frac{1}{4{\pi ɛ}}\left\lbrack {{\Sigma_{k^{\prime} = 0}^{k}\frac{{Qt}_{k\; \prime}^{m + 1 - {({k - k^{\prime}})}} - {Qt}_{k}^{m + 1}}{k - {k\; \prime}}} + {\Sigma_{k^{\prime} = {k + 1}}^{N}\frac{{Qt}_{k\; \prime}^{m + 1 + {({k - k^{\prime}})}} - {Qt}_{k}^{m + 1}}{- \left( {k - k^{\prime}} \right)}}} \right\rbrack}\mspace{76mu}\left\lbrack {{Math}.\mspace{14mu} 18} \right\rbrack}} & (19) \\ {{{}_{}^{}{}_{k + {1\text{/}2}}^{m + {1\text{/}2}}} = {\frac{\mu}{4\pi}\left\lbrack {{\Sigma_{k^{\prime} = 0}^{k}\frac{{It}_{k^{\prime} + {1\text{/}2}}^{m + {1\text{/}2} - {({k - k^{\prime}})}} - {It}_{k + {1\text{/}2}}^{m + {1\text{/}2}}}{k - {k\; \prime}}} + {\Sigma_{k^{\prime} = {k + 1}}^{N}\frac{{It}_{k^{\prime} + {1\text{/}2}}^{m + {1\text{/}2} + {({k - k^{\prime}})}} - {It}_{k + {1\text{/}2}}^{m + {1\text{/}2}}}{- \left( {k - k^{\prime}} \right)}}} \right\rbrack}} & (20) \end{matrix}$
 8. The method for calculating the potential, the current, and the peripheral electromagnetic field in the electric circuit according to claim 7, wherein the obtaining of the potential and the current in the multi-conductor transmission line performs: in m=0, calculating Uv₀ ¹ and vI₀ ¹ by Equation (16); calculating Qt₀ ¹ by Equation (18); calculating ˜U₀ ¹ by Equation (19); calculating Qt_(k) ¹ (k=1, 2, . . . , N−1) by Equation (18); calculating ˜U_(k) ¹ (k=1, 2, . . . , N−1) by Equation (19); calculating Uv_(k) ¹ (k=1, 2, . . . , N−1) by Equation (7); calculating Uv_(N) ¹ and vI_(N) ¹ by Equation (17); calculating Qt_(N) ¹ by Equation (18); calculating ˜U_(N) ¹ by Equation (19); calculating ˜A_(k+1/2) ^(1/2) (k=0, 1, . . . , N−1) by Equation (20); and calculating Iv_(k+1/2) ^(3/2) (k=0, 1, . . . , N−1) by Equation (8), and in m≥1, calculating Uv₀ ^(m+1) and vI₀ ^(m+1) by Equation (16); calculating Qt₀ ^(m+1) by Equation (18); calculating ˜U₀ ^(m+1) by Equation (19); calculating Qt_(k) ^(m+1) (k=1, 2, . . . , N−1) by Equation (18); calculating ˜U_(k) ^(m+1) (k=1, 2, . . . , N−1) by Equation (19); calculating Uv_(k) ^(m+1) (k=1, 2, . . . , N−1) by Equation (7); calculating Uv_(N) ^(m+1) and vI_(N) ^(m+1) by Equation (17); calculating Qt_(N) ^(m+1) by Equation (18); calculating ˜U_(N) ^(m+1) by Equation (19); calculating ˜A_(k+1/2) ^(m+1/2) (k=0, 1, . . . , N−1) by Equation (20); and calculating Iv_(k+1) ^(m+3/2) (k=0, 1, . . . , N−1) by Equation (8) repeatedly until a value of m reaches a predetermined value while incrementing m by
 1. 9. A program for causing a computer to execute the method for calculating the potential, the current, and the peripheral electromagnetic field in the electric circuit according to claim
 1. 